Dial pulse measurement circuitry

ABSTRACT

A method for analysis of rotary dial pulses focuses on transitions between pulse levels and differentiates true level changes from noise using a procedure employing two sample counters. One counter registers the number of consecutive samples at either the high or low levels and, once a predetermined number of consecutive samples are detected, a corresponding high or low level is declared. However, since noise may influence the detection, the total number of samples, from the first indication of a level change until the declaration of a state, is maintained in a second counter. A false transition reinitializes both counters, while level changes yielding less than the predetermined number only reinitialize the first counter.

REFERENCE TO A MICROFICHE APPENDIX

This application contains a set of microfiche appendices, designated Aand B, listing programs incorporated in the testing system comprisingthe subject matter of this disclosure. The total number of microfiche is18 and the total number of frames is 1055.

CROSS-REFERENCE TO RELATED APPLICATIONS

The following U.S. applications, which are assigned to the same assigneeas the instant application and filed concurrently therewith, haverelated subject matter. Certain portions of the system, processes andcircuitry herein disclosed are inventions of the below named inventorsas defined by the claims in the following patent applications:

(1) "Mechanized Testing of Subscriber Facilities", Ser. No. 399,177 ofH. Rubin;

(2) "Data Communication Network", Ser. No. 399,186 of C. L. Coleman-H.Rubin;

(3) "Networks for Data Communication", Ser. No. 399,180 of H. Rubin;

(4) "Message Routing though Data Communication Networks", Ser. No.399,187 of N. R. Fildes;

(5) "Parallel Bus Protocol", Ser. No. 399,171 of N. R. Fildes;

(6) "System for Accessing and Testing Subscriber Loops", Ser. No.399,185 of H. Rubin;

(7) "Switching Network for Interactive Access and Testing of SubscriberLoops", Ser. No. 399,188 of H. Rubin;

(8) "Stored Program Controller", Ser. No. 399,175 of H. Rubin;

(9) "Programmable Tester for Measuring Network Characteristics", Ser.No. 399,172 of H. Rubin;

(10) "Programmable Network Tester with Data Formatter", Ser. No. 399,184of K. B. Kemper-H. Rubin;

(11) "Programmable Gain Amplifier", Ser. No. 399,183 of K. B. Kemper;

(12) "Digital Signal Generator", Ser. No. 399,176 of H. Rubin;

(13) "Magnetic Current Sensor", Ser. No. 399,182 of K. B. Kemper;

(14) "Magnetic Current Sensor with Offset and Load Correction", Ser. No.399,174 of J. M Brown-K. B. Kemper;

(15) "Magnetic Differential Current Sensor Ser. No. 399,173 of J. M.Brown;

(16) "Digital Filtering with Monitored Settling Time", Ser. No. 399,189of H. Rubin;

(17) "Coin Telephone Measurement Circuitry", Ser. No. 399,178 of H. A.Miller;

(18) "Dual-port Random Access Memory Arrangement", Ser. No. 399,179 ofH. C. Bond-E. H. McFadden-H. A. Miller.

TABLE OF CONTENTS

Technical Field

Background of the Invention

Summary of the Invention

Brief Description of the Drawing

Detailed Description

1. THE MECHANIZED LOOP TESTING (MLT) ARCHITECTURE

2. MLT IMPLEMENTATION

2.1 Data Communication Network (DCN)

2.1a Structure

2.1b Message Routing

2.1c Software Design

2.1d Software Operation

2.2 Loop Testing System (LTS)

2.2a Structure

2.2b LTS Operation

2.2.1 LTS Controller

2.2.1a Access Request Processing

2.2.1a.1 Regular Test Access and MDF Trunk Access

2.2.1a.2 Interactive Access Request Processing

2.2.1a.3 Callback Access Processing

2.2.1b Test Request Accessing

2.2.1c LTS Requests

2.2.1d LTS Controller Circuitry

2.2.2 Port Controller

2.2.3 Precision Measurment Unit (PMU)

2.2.3a Digital Signal Generator (DSG)

2.2.3b Magnetic Current Sensor

2.2.3c Signal Processing

2.2.3d PMU Controller

2.2.4 LTS Circuits For Establishing Loop Connections

2.3 Front End (FE) System

3. MLT CIRCUITRY AND PROGRAMS

3.1 DCN Implementation

3.1.1 Circuitry

3.1.2 DCN Programs

3.2.1 LTS Controller Implementation

3.2.1a LTS Main Controller Circuitry

3.2.1b LTS Universal Memory

3.2.1c LTS Serial Data Line Interface

3.2.1d LTS Programs

3.2.1e Test Sequences

3.2.2 Port Controller Implementation

3.2.3 PMU Implementation

3.2.3a DSG Circuitry

3.2.3a.1 DSG Software Considerations

3.2.3a.2 DSG Hardware Considerations

3.2.3b Magnetic Current Sensor Circuitry

3.2.3c Digital Processing and Control

3.2.3d Digital Processing Considerations

3.2.4 Loop Connection Circuitry

3.3 FE System Considerations

TECHNICAL FIELD

This invention relates generally to testing of telecommunicationfacilities such as telephone loops provided over multipair cables and,more particularly, to a stored program control system which directs anetwork of distributed processors to access and measure the facilities.

BACKGROUND OF THE INVENTION

In order to test telephone loops, whether for fault diagnosis,preventive maintenance purposes or even to compile statisticalinformation about loop characteristics, three basic functions arerequired, namely: access, test and communication. These three basicfunctions can readily be identified for any manual or automatic testingsystem. For instance, within each system, there are mechanisms forgaining control of a loop to be tested, for connecting to it and fordirecting appropriate testing activities. Moreover, a two-waycommunication path exists between testing personnel or equipmentinterfaces so that selected test activities may be initiated,coordinated and the results collected for analysis. Oftentimes, anautomated central controller determines the testing pattern and analyzesresults via interpretive algorithms.

One such computer-based system has been described in an article entitled"The Evolution of the Automated Repair Service Bureau with Respect toLoop Testing", published in the Conference Record of the InternationalSymposium on Subscriber Loops and Services, March, 1978, pages 64-68 asauthorized by O. B. Dale. The Automated Repair Service Bureau (ARSB),which supports loop maintenance operations, includes the followingmaintenance functions: receiving trouble reports from customers; troublereport tracking; generating management reports; and real-time looptesting and fault diagnosis. Thus, within the ARSB framework, there isprovided a rapid, convenient method for testing and analyzing testresults automatically at the time of customer contact as well as ondemand during repair procedures.

In order that the subject matter of the present invention may beelucidated, it is important to elaborate on the ARSB architecture andthe capabilities of the above-mentioned testing arrangement within thisarchitecture. The information presented by this overview is set forth inthe above-mentioned reference as well as in an article entitled"Automation of Repair Service Bureau", Conference Publication No. 137 ofthe International Symposium on Subscriber Loops and Services, May, 1976as authored by R. L. Martin. FIG. 1 indicates that the coventional ARSBcomprises a tree-like structure with four major levels. At Level 1 ofthe tree is a data storage computer (200) which maintains a master database of up to five million customer line records; the information onthese records includes data as to equipment terminating the loop, loopcomposition, customer telephone number, and so forth. Level 2 iscomposed of an array of front end (FE) computers (220,221), each ofwhich manages the bulk of the trouble report processing for about500,000 lines. The users of the system, typically maintenance and craftpersonnel of the telephone company deploying the ARSB, interact with thesystem at this level. Level 3 is an array of control computers (240,241)that control access and testing and provide analysis of test results.Level 4 comprises loop testing frames (250,251) which perform the loopaccesses and actual test measurements via test trunk connections toswitching machines located in geographically-dispersed central offices.

Test requests from users are received and supervised by the FE computersand then performed by algorithms in the control computers and circuitryin the loop testing frames. The tests conducted are based on adaptivealgorithms that compose test scripts in real time as a function of theelectrical characteristics of the customer's equipment in the idlestate. The data used are extracted from the data storage computer andthen provided by the FE computers at the time the test request isgenerated. As testing on a customer's loop proceeds, the test script iscontinually being revised to reflect the knowledge of the loop which hasbeen gained from the test results. The final test results and analysisare formatted for display to the user by the requesting FE computer.Varying levels of display detail, based on the technical sophisticationof the user, are provided.

The loop testing subsystems of the ARSB were arranged to provide anarea-based (about 1 million loops) system in order to expedite itsintroduction and mitigate cost to users. As a result, not all of thetesting functions of the standard pre-ARSB facility, known as the LocalTest Desk (LTD), were incorporated. For instance, the LTD continued tobe used for interactive testing between testers at the LTD and fieldrepair craft. The loop testing subsystem could not be utilized tomaintain a connection to the loop under test for a prolonged duration,nor could field repair personnel be guided through a series of steps todiagnose, locate and correct a fault. In short, the loop subsystem waseffective only in screening troubles and performing pre-dispatch andpost-dispatch testing. Also, not every type of terminal equipment couldbe tested. For instance, coin telephone features were precluded fromtesting. Moreover, because the LTD operated within the same environmentas the ARSB, the LTD was considered a backup during temporary outages ofARSB so there was no need for redundancy or fail-soft operation in thetesting system. Finally, the area-oriented system was not cost effectivefor single wire centers serving only a few thousand lines.

With the above background, the significant limitations and deficienciesof the conventional ARSB testing system, including those emphasizedabove, may be summarized as follows: (1) no interactive testingcapability with field craft personnel nor customers; (2) inability totest coin telephone stations including such conditions as off-normaltotalizers, stuck coin conditions, coin collect and coin returncircuitry, and loop-ground resistance; (3) impossible to test and talkover the same test connection; (4) no single- and double-sided resistivefault sectionalization capability; (5) no ability to apply metallic orlongitudinal pair identification tones; and (6) no capability to controland monitor concurrent testing operations from a single work station.

Besides the ARSB approach, numerous other automated, but less complex,approaches have been employed to effect loop testing. Typically thesehave focussed on specialized problem areas, such as rapid-scanprocedures to verify the accuracy and quality of splicing operations orsimplified checks on easily quantifiable loop parameters like loopinsulation resistance or loop impedance at a given frequency forpreventive maintenance purposes.

Other automated approaches, with a sophistication comparable to the ARSBapproach, have been developed for the purpose of diagnostic testing. Onerepresentative prior art system is disclosed in U.S. Pat. No. 4,139,745issued to Ashdown et al on Feb. 13, 1979. Broadly speaking, the systemcomprises control means having a programmed digital computer andassociated memory, a line test network, at least one user station and aninterface for interconnecting these elements and one or more telephoneexchanges and the plurality of telephone lines extending from suchexchanges.

The line test network is responsive to the digital computer and incluesmeans for generating a plurality of signals for a test cycle. During acycle, besides DC and noise measurements, AC signals are applied to thethree-wire line comprising the tip-ring-ground conductors andlongitudinal and metallic response signals are measured. The responsesare utlized to provide an indication of the capacitive load across theline which, in turn, may be translated to produce parameters indicativeof, for example, line length, type of termination and possible linefaults.

However, this prior art system possesses the same shortcomings andlimitations summarized above with respect to the ARSB. Moreover, sincethe system is not comprised of a data base for storing information aboutline compositions, adaptive testing and interpretation of results inview of line configuration information is precluded. In addition,although many users may have access to the system, each testingoperation is basically sequential and there is no suggestion that accessand testing operations on many different lines within one exchange maybe occurring concurrently.

It is clear from a persual of the prior art portion of the ARSB setforth in FIG. 1 that each grouping of test trunks is served by only oneFE computer. In the event of a FE computer outage, the Local Test Deskcould, temporarily, satisfy user test requests. However, such reliancereduces system throughput and is inappropriate in a fully automatedtesting environment. Such a shortcoming is obviated in an architecturethat allows a plurality of FE computers to access any particular trunk.

To mitigate these and similar shortcomings, some distributed computersystems require that a cluster of controlling minicomputers communicatewith remote entities that typically include microprocessor-basedsubsystems. However, when the number of such remote entities becomelarge, a significant amount of minicomputer processing time must bedevoted to these communication needs, and throughput is again reduced.

Also, packet switching networks may be used advantageously in somesituations, but delay times through such networks and the cost ofadditional remote circuitry can render these solutions unattractive.

With the development of microprocessors, which function autonomously, itbecomes feasible to decentralize switching functions and thereby offloadmany controller computer communication activities to the actual point ofswitching. Such an arrangement is discussed in U.S. Pat. No. 4,285,037issued to H. Von Stetten on Aug. 18, 1981; this disclosure is selectedas representative of numerous distributed processor switching networksconfigured for intercomputer communication. In these networks, alldistributed processors, generally microprocessors, are connected to oneanother via a common bus. Communication of messages in the transmittingand receiving directions occurs between the processors in the form ofinformation blocks having address information. A central clock isprovided under whose control respective processors are cyclicallyconnected for the emission of an information block and all otherprocessors are connected to the common data bus in the receiving mode.Only the receiver having the specified address then receives the desiredmessage. The processors comprising the system receive information fromand transmit messages to associated peripheral or interface devices. Forinstance, some processors may be coupled to terminals or memories,whereas other processors may connect to communication lines havingdifferent baud rate capabilities.

The major shortcomings of such an arrangement include the utilization ofa common bus which precludes alternative routing in case of a busfailure and the sequencing procedure allowing only one bus talker at atime. During peak message transfer periods, such an allocation procedurecould lead to blocking situations with concomitant throughput delays.

Also, the standard communication sequences between a sender and receiverover a bus are usually replete with segments of no activity on the bus.For instance, after the sender transmits a message, the receivercomputes a check word while the sender remains idle. The receiver thenreturns an acknowledge/negative acknowledge status message. Once thetransmitted message is accepted, the sender then determines the nextactivity while the receiver is now inactive. Techniques have beendevised to improve the efficiency of transmission in this simplesender-receiver situation. One such improvement utilizes the time thesender is idle (during check word computation) to effect a determinationof the next activity.

The inefficiency is magnified in the situation of a talker communicatingwith many listeners. During the period in which one receiver iscomputing a check word, the remaining receivers are idle. If aretransmission is necessary, the inefficiency is compounded. Part of thedifficulty occurs because the accept-reject status of a total message isalso formulated as a message and returned over the data leads of thebus. Moreover, in situations exemplified by the MLT sytem, wherein themessage propagate time is of the same order as a check word computation,the sender is idle for a significant portion of each transmissionactivity. This is in contrast to the situation wherein the messages areconsiderably longer than the check word computations, so the percentageof time the sender is idle is small.

As alluded to above in the summary of ARSB deficiencies, automatedtesting of coin telephone systems has, in the past, presented severeimplementation problems because of the special nature of the coinequipment. Other special loop situations, such as analysis of dialpulses or measurement of nonlinear devices like thermistors, have alsopresented basically insurmountable implementation difficulties withconventional automated test procedures and equipment. Fortuitously,however, technological advances recently occurred which now make itpossible to solve these problems and difficulties. Advances inmicrocomputing, digital signal processing and measurement technologyhave provided the motivation for the development of versatile digitalsignal generators and digital analysis techniques, including digitalfiltering, which produce rapid and accurate measurements. Unfortunately,however, the majority of subscriber lines to be tested are still analogin nature and parameters of interest relate to the frequency-dependentcharacteristics of the lines. Therefore, a suitable transponder forinterfacing the analog lines to the sophisticated digital processingtechniques is still a fundamental necessity.

One such transponder arrangement developed for sensitive line currentmeasurements is disclosed in U.S. Pat. No. 4,274,051 issued to J. Condonon June 16, 1981. The invention set forth in this reference utilizes apair of magnetic structures to produce an output signal when the currenton the loop is other than zero. However, because the line currentsundergoing measurement with this arrangement were large in magnitude,the errors caused by differences in the hysteresis characteristicsbetween structures were negligible and could be ignored. Such errors,particularly when measuring differential currents, prove to be criticaland require compensation to insure accuracy and resolution over thebroad operating range expected of the transponder in the digitalprocessing environment.

SUMMARY OF THE INVENTION

In accordance with the illustrative embodiment of the present invention,a procedure is disclosed for analyzing telephone rotary dial pulses toestablish make/break intervals for fault diagnosing purposes. Tomitigate false declarations of pulse level changes in the presence ofinterference and transients, the procedure concentrates on the finestructure of a potential transition interval while maintaining data overan extended period initiated by the first indication of a level change.

The signal, composed of dial pulses degraded by noise, is sampled andeach sample of the sequence is classified as a high level sample or alow level sample by comparison to a threshold. The sequence from theclassifier is monitored for a high-to-low or low-to-high transitiondepending on the command transmitted from the requesting controller orthe previous state of analysis. Once a transition is detected, a firstregister counts the samples until a predetermined number of consecutivesamples have attained the same level. If this level is not the oneanticipated, a false transition is declared and the first register isreinitialized and monitoring continues. If this level indicates a changehas occurred, a transition is declared. The first register transfers itscontents to a second register, the second register continues countingsamples, and the first register is reinitialized to begin a new search.The time duration of a level is proportional to the contents of thesecond register less the predetermined number.

The invention is set forth with particulaity in the appended claims. Anunderstanding of this invention may be obtained with reference to thefollowing detailed description taken in conjunction with theaccompanying drawing.

BRIEF DESCRIPTION OF THE DRAWING

FIG. 1 indicates the architectural arrangement of one conventionalautomated testing system and, in accordance with an alternativeembodiment of the present invention, an arrangement for integrating thedistributed Mechanized Loop Testing (MLT) system within the conventionalsystem to expand test capabilities.

FIG. 2 depicts, in overview fashion, a block diagram of the majorcomponents comprising the stand-alone Mechanized Loop Testing system, aswell as the interconnections among these components.

FIG. 3 depicts a three-tier multiprocessor realization of the DataCommunication Network (DCN) shown in block diagram form in FIG. 2.

FIG. 4 illustrates the internal bus structures of the connection matrixand the connection arrays of the DCN.

FIG. 5 shows the flag-field pattern for a reprsentative conventionalhigh level data link protocol and, in particular, the location of theINFORMATION field within the pattern.

FIG. 6 indicates the composition of the INFORMATION field in terms ofHEADER parameters and DATA bytes utilized by the MLT system in messagerouting, loop access and loop test.

FIGS. 7, 8 and 9 show the microcomputer software architecture, inpictorial form, for tiers 1, 2 and 3, respectively, of the DCN. Theseillustrations are pictorial in the sense that they indicate a logicalsituation in terms of the number of copies of software utilized toimplement the various system tasks.

FIG. 10 depicts the priority of execution of tasks within any of themicrocomputers of the DCN. Both the initialization execution (topportion of FIG. 10) and execution with external event interrupts areillustrated.

FIG. 11 depicts, in block diagram form, a realization of the LoopTesting System (LTS) shown pictorially in FIG. 2.

FIG. 12 illustrates the DATA bytes in the INFORMATION field for theregular or main distributing frame access request message as routedthrough the LTS of FIG. 11.

FIG. 13 illustrates the contents of an interactive request message whenboth a loop access and a talk path to the Maintenance Center are to beestablished.

FIG. 14 depicts the message returned from the port controller of FIG. 11in response to an access request message.

FIG. 15 illustrates those DATA bytes extracted from the message formatof FIG. 13 which are then utilized by the TCD task of the LTS controllerof FIG. 11 to establish the actual callback path.

FIG. 16 is a depiction of the message format for a test request.

FIG. 17 depicts, in block diagram form, the circuitry comprising onePrecision Measurement Unit (PMU) of FIG. 11.

FIG. 18 is a more detailed representation of the PMU controller, AC-DCsource generator and digital signal processing portions of the blockdiagrams of FIG. 17.

FIG. 19 illustrates the arrangement of memory bytes to realize theaccumulator of the digital signal generator within the AC-DC sourcegenerator of FIG. 17.

FIG. 20 is a diagram, partly in schematic and partly in block form,showing one implementation of the source applique of FIG. 17.

FIG. 21 indicates essential portions of magnetic current sensorcircuitry of the detector portion of FIG. 17 whereby loop currents aretransformed to equivalent voltages.

FIG. 22 depicts the processing circuitry of the detector of FIG. 17utilized to filter and scale the equivalent voltages.

FIG. 23 shows a block diagram representation of the measurementprocessor of FIG. 17.

FIG. 24 indicates the manner in which FIGS. 18, 20, 22 and 23 may bearranged to form a composite representation of FIG. 17.

FIG. 25 indicates that the PMU task provides data to specify which ofthe many possible test requests is to be selected and, accordingly,appropriate parameters are passed to the measurement cycle controller.

FIG. 26 depicts the sequencing of the measurement cycle controller foreach configuration of PMU circuitry.

FIG. 27 illustrates the switch matrices comprising the equipment accessnetwork of FIG. 17 as well as the arrangement of various access and testcircuits of FIG. 17 at the ports of the equipment access network.

FIG. 28 indicates that: a tier 1 device in the DCN is composed of thecircuitry depicted in FIGS. 29 and 30; a tier 2 interface is formed fromthe circuitry of FIGS. 29 and 30; and a tier 3 circuit comprises thecircuitry of FIGS. 29, 32 and 33.

FIG. 29 is a block diagram representation of the CPU circuitry utilizedby the three tiers of the DCN.

FIG. 30 is a block diagram illustration of the serial-input,parallel-output communication circuitry of a tier 1 device.

FIG. 31 is a representation in block diagram form of theparallel-to-parallel communication circuitry of a tier 2 interface.

FIG. 32 depicts the parallel-input portion of a tier 3 circuit in blockdiagram form, whereas FIG. 33 shows the serial-output portion of eachtier 3 circuit.

FIGS. 34 through 36 and 38 through 41 are schematics of the varioussubsystems comprising the CPU circuit of FIG. 29 and include,respectively: the reset circuitry; the interrupt structure; themicrocomputer-based processor; address buffer; random access memory;address decoder; and timer, buffer and circuitry identifierarrangements.

FIG. 37 is a timing diagram indicating the levels of the ports of themicrocomputer relative to the input clock.

FIG. 42 depicts the signal leads comprising the three external bussesand the internal bus shown in FIG. 29.

FIGS. 43 through 48 are schematics of the different subsystemscomprising the serial-to-parallel portion of a tier 1 device shown inFIG. 30 and include, respectively: read-only memory;talker/lister/controller interface; direct memory access circuits withaccompanying data buffer; data link protocol interfaces with associatedbuffer; and chip select circuitry.

FIGS. 49 through 53 are schematics of the subsystems cooperating to formthe parallel-to-parallel portion of a tier 2 interface shown in FIG. 31and include, respectively: talker/listener interface; direct memoryaccess circuitry; and chip select circuitry.

FIGS. 54 and 55 are schematics of the serial output portion and theprogrammable interval timer portion, respectively, of a tier 3 circuitshown diagrammatically in FIG. 33.

FIG. 57 is a depiction of the interconnection between a controller andlistener explicitly setting forth the serial poll register contents andthe major/minor addressing capability of the general purpose bus.

FIG. 58 indicates that: the LTS controller of FIG. 11 is comprised ofthe circuitry depicted in FIGS. 59, 69 and 72; the port controller ofFIG. 11 is a composite of the circuitry shown in FIGS. 59, 69 and 81;the PMU controller of FIG. 17 is formed from the circuitry illustratedin FIGS. 59 and 69; and the digital signal processing circuitry of FIG.17 is depicted by the block diagram of FIG. 110.

FIG. 59 is a block diagram representation of the CPU circuitry utilizedto implement either the LTS main controller, port main controller or thePMU main controller.

FIGS. 60 through 68 are schematics of the different modules forming thebasic main controller as depicted by FIG. 59 and include, respectively:the microprocessor and its associated controller as well as bus buffers;timer and bus adapter; bus controller and associated buffers as well assystem reset; system oscillator and clock divider; and two types ofrandom access memory.

FIG. 65 depicts the signal leads comprising the external and internalbusses shown in FIG. 60.

FIGS. 66 through 68 indicate the memory allocation, including thosebank-switched portions, for the LTS controller, the port controller andPMU controller, respectively.

FIG. 69 is a block diagram of the universal memory board which indicatesthat FIG. 70 provides the schematic diagrams for the data transceiver,address buffer and decoder as well as the bank selector portions of theuniversal memory whereas FIG. 71 provides the arrangement of memorydevices.

FIG. 72 is a block diagram of the data line interface associated withthe LTS controller of FIG. 58.

FIGS. 73 through 75 are schematics of the subcomponents comprising thedata line interface of FIG. 72 and include, respectively: read-onlymemory and random access memory realizations as well as address decodingfor these memories; synchronous data link protocol controller andassociated clock; and reset and data buffer circuitry.

FIG. 76 is a block diagram representation of circuitry arranged toeffect a measurement of loop balance.

FIG. 77 incorporates both schematic and block diagram illustrations toindicate the procedure for measuring metallic noise in LOOP, RING groundand TIP ground start central offices.

FIG. 78 indicates an arrangement for detecting a single frequency toneon a subscriber loop.

FIG. 79 presents circuitry for rotary dial analysis.

FIG. 80 is a representation of a circuit utilized to test for receiveroff-hook conditions.

FIG. 81 is a block diagram of the port interface associated with theport controller of FIG. 58; this diagram indicates that circuit detailsrelating to the address decoder are given in FIG. 82 whereas FIG. 83presents random access memory realizations.

FIG. 84 is a block diagram depiction of circuitry comprising the ACportion of the source generator of FIG. 18.

FIG. 85 is a more detailed representation of one AC reference signalgenerator depicted in FIG. 84.

FIG. 86 is a structure chart indicating the calling linkages among thevarious processes, output functions and subroutines comprising theprograms of the AC generators of FIG. 84.

FIGS. 87 and 91 are flow charts for the RESET process and the DATAACCEPT subroutine depicted in FIG. 86, whereas FIGS. 88 through 90provide the flow chart for the NMI process.

FIG. 92 illustrates the data transfer sequence for a variable byte countrelating to providing information to the Sequence Single Frequencyoutput function.

FIG. 93 depicts the bit weights to be assigned to the hexidecimal datavalues for digital signal generation.

FIG. 94 indicates the number and order of transmission of bytes for thevarious output functions of the source generator.

FIG. 95 is a flow chart of the program implementing the Single Frequencyoutput function.

FIG. 96 is a recasting of FIG. 20 in view of the circuit detailspresented for the source generator.

FIG. 97 is a flow diagram for the SINCOS subroutine.

FIGS. 98 and 99, in combination, present the flow chart for the SequenceMultifrequency function.

FIGS. 100 through 103 are flow charts for, respectively, ConvertFrequency, Zero, T-ON and T-OFF subroutines of the source generator.

FIG. 104 is a memory map for the various software routines utilized toimplement the source generator of FIG. 17.

FIG. 105 combines the circuitry of FIGS. 20 and 21 which allow a fullelucidation of the operation of the magnetic current sensor circuitry.

FIGS. 106 and 107 present a portion of major saturation hysteresis loopfor two magnetic structures implementing a current sensor for matchedand mismatched conditions, respectively.

FIG. 108 is a diagram indicating the sequence of operations, as well astheir relative timing, for generating a pair of data samples in themeasurement processor of FIG. 11.

FIG. 109 depicts circuitry implementing a programmable gain amplifierfor autoranging during a measurement cycle.

FIG. 110 is a block diagram of the digital signal processor depictedwith reference to the PMU circuitry of FIG. 58.

FIGS. 111 through 114 are schematics of the different subcomponentscomprising the digital signal processor of FIG. 110 and they indicate,respectively: random access memory and read-only memory implementations;the dual-port RAM and demultiplexing circuitry to interface the PMUcontroller to the programmable signal processor of FIGS. 112 and 114;and address decoding circuitry.

FIG. 115 shows the architectural arrangement for the special purposesignal processor implementing the down-loaded signal processingtechniques.

FIG. 116 illustrates the boundary alignment for the various registersand busses comprising processor of FIG. 115.

FIGS. 117, 118 and 119 depict the flow diagram of a program for digitalfiltering DC signals and thereby determine the settled DC values for oneto six synchronously demodulated channels.

FIGS. 120 through 123 depict the flow diagram of a program for analyzingcoin phone tone bursts in order to test a coin totalizer.

DETAILED DESCRIPTION

1. THE MECHANIZED LOOP TESTING (MLT) ARCHITECTURE

The overriding architectural consideration employed in the MLT system isto distribute the access, test and communication functions as closely aspossible to the point of testing, which generally is the centralizedswitching facility serving the subscriber loops to be tested. Thedeployment of such a distributed architecture minimizes data flow in thesystem, increases testing accuracy and expands test capabilities.

To place in perspective the description that follows, FIG. 1illustrates, in overlay fashion, one arrangement for integrating thedistributed MLT system within the framework of the ARSB system discussedin the Background Section. In this depiction, it is clear that oneembodiment of the MLT system serves as an adjunct to the testing systemdescribed earlier. However, the illustrative embodiment of the presentinvention is best elucidated as a stand-alone system and thisarrangement is shown in FIG. 2.

FIG. 2 depicts, in overview fashion, a block diagram of an illustrativeembodiment of the MLT architecture arranged in accordance with thepresent invention. Data storage computer 200 stores information abouteach subscriber loop existing in the area to be served by the MLTsystem. For instance, typical types of information accessible incomputer 200 include the composition of the subscriber loop, officeequipment, outside plant equipment and terminating equipment associatedwith each loop.

The area served by a MLT system generally encompasses a number ofgeographically-dispersed wire centers 150 and 151 containing switchingmachines 170 and 171, respectively. Individual subscriber loops 180, . .. , 183, with associated customer equipment 190, . . . , 193,respectively, are served by wire centers 150,151 and connect toswitching machines 170,171. Each wire center 150 or 151 served by theMLT system contains a collocated microprocessor-based Loop TestingSystem (LTS), 160 or 161, respectively, that also implements access,test and communication capabilities (shown pictorially as components ofeach LTS 160 or 161 in FIG. 2). The access portion of each LTS 160,161is arranged with circuitry for establishing a transmission connection,under control of FE computers 220,221, over the national dial network,that is, the Direct Distance Dialing (DDD) network, via facilities 932and 933 emanating from wire centers 150 and 151, respectively. Switchingmachines 170,171 are accessible from LTS 160,161 via test trunks940,941, respectively.

Front-end (FE) computers 220,221 interact with storage computer 200 toretrieve pertinent data regarding subscriber loops to be tested. SinceFE computers 220 and 221 are not necessarily collocated with computer200, data links 900 and 901, respectively, are provided forintercomputer communication. Direct communication between FE computers220,221 is accomplished via Parallel Communication Link (PCL) 210 andinterposed busses 910,911, respectively.

The communication functions that reside in each LTS 160,161 and in eachFE computer 220,221 are coupled via Data Communication Network (DCN)140. DCN 140 allows any one of FE computers 220,221 to communicate withany LTS 160,161 in any wire center 150,151 served by the MLT system. DCN140 is also a microprocessor-based distributed processing machine thatoffloads communication processing for all FE computers 220,221.

The architecture depicted in FIG. 2 allows any FE computer 220,221 totest any customer loop 180, . . . , 183 within the area served by theMLT system. To demonstrate this, the following describes, again inoverview fashion, the operation of the illustrative embodiment of theMLT system.

A loop test is typically generated by a request from repair servicebureau personnel, typically a maintenance administrator. This user has aconsole 230,231 with an input/output device, e.g., a keyboard andcathode-ray tube (CRT), for interfacing to a FE computer 220,221 viadata links 912,913, respectively; the console also includes circuitry235,236 for communicating over the DDD network via conventionalfacilities 914 and 915. Several types of CRT masks are available toenable the user to input data (e.g., a telephone number to be tested)and receive output (e.g., test results) from the MLT system. When theuser determines a subscriber loop is to be tested, an MLT programresident on FE computer 220 or 221 requests that certain data baseinformation be retrieved from storage computer 200 relating to thecharacteristics of a loop 180, . . . , or 183 to be tested. Thisinformation is utilized by an application process resident on FEcomputer 220 or 221 that initiates accessing of the loop and then guidesloop testing. The application process may contain, for instance, anadaptive loop testing algorithm or it may contain commands to implementinteractive test control and other functions similar to that performedwith manual testing.

Because of the processing capability available in the microcomputers ofLTS 160,161, only high level commands are generated by FE computers220,221. The first command requests LTS 160 or 161 to access a specifiedtelephone number and, if interactive testing is required, the commandalso provides the telephone number of the circuitry at the user'sconsole so a callback path may be established. The message compiled bythe appropriate FE computer 220 or 221 to implement the command andtransmitted over outgoing data link 920 or 921 contains a message fieldhaving a parameter that identifies which LTS data link 930 or 931 is tobe utilized for intercomputer communication. Any message, including thefirst one, is routed from FE computer 220 or 221 to DCN 140 via incomingdata links 920 or 921 and, after appropriate parsing and reassembly ofthe message, from DCN 140 to the preselected LTS 160 or 161 via outgoingdata link 930 or 931. When access is completed, the response is reroutedthrough data link 930 or 931, DCN 140 and data link 920 or 921 to the FEcomputer 220 or 221 that requested the access. Subsequent messagetransactions that occur between FE computer 220 or 221 and LTS 160 or161 involve high level requests for tests to be performed, followed bydetailed responses containing raw test data (e.g., the amount of currentthat was measured on loop wires 180, . . . or 183 when a particularsource was applied to the loop by LTS 160 or 161). These transactionsmay be prefaced with oral communications between the maintenanceadministrator at console 230,231 and the customer serviced by the loopor field craft personnel at a location along the loop. Thesecommunications are transacted over DDD callback path and are generallyutilized in the interactive test mode to establish appropriateconditions on the loop for test purposes. For example, a craftperson maybe requested to short the loop so a DC resistance measurement may beeffected. The last request made by FE computer 220 or 221 is to have LTS160 or 161 disconnect from loop 180, . . . or 183 under test. The numberof loops that may be accessed simultaneously at any LTS site and thenumber of simultaneous tests that may be in progress at a given LTS arediscussed in the sequel.

The above overview shows the basic design philosophy of the MLT systemand illustrates one distributed processing approach to loop testing.Hardware and software functions are partitioned so that systemcomplexity is reduced to the point where basically independentlydesigned and maintained modules interact via high level commands. Thefollowing section describes the individual modules or components of theMLT system in somewhat more detail, but basically still in overviewfashion, from both a hardware and software perspective. After this,another pass through each component will complete the detaileddescription.

2. MLT IMPLEMENTATION

2.1 Data Communication Network (DCN)

2.1a Structure

As indicated in FIG. 2 and alluded to in the foregoing discussion, DCN140 is structured to route messages between any FE computer 220,221 andany LTS 160,161. The illustrative embodiment of DCN 140 to be describedallows from one to twelve FE computers to exchange data with up to sevenhundred and sixty eight (768) Loop Testing Systems. (This capacity isdetermined by anticipated user needs; the total capacity of thearchitecture of DCN 140, without bus extenders, is actually 1568 datalinks or, equivalently, 1568 Loop Testing Systems.)

FIG. 3 shows a three-tiered mutliprocessor realization of DCN 140. Tier1 serial-in, parallel-out devices 1401, . . . , 1412 are arranged toaccept incoming data links 9201, . . . , 9224 on a two datalink-per-device basis. For instance, device 1401 in tier 1 interconnectsto data links 9201 and 9202. Incoming data links 9201, . . . , 9224originate from FE computers 220,221 of FIG. 2. In fact, internal datalink 9201 is the same link identified as external data link 920, asdepicted in FIG. 3. A similar identification may be made between links921 and 9224.

Tier 3 parallel-in, serial-out processing circuits 14001, . . . , 14096are arranged to provide outgoing data links 93001, . . . , 93768 on aneight data links-per-circuit basis. Outgoing data links 93001, . . . ,93768 terminate on LTS's 160,161 of FIG. 2. In fact, internal data link93001 is the same link identified as external link 930, as depicted inFIG. 3. A similar identification may be made between links 931 and93768.

Tier 2 parallel-in, parallel-out processing interfaces 1421, . . . ,1468 serve to interconnect first tier devices 1401, . . . , 1412 andthird tier circuits 14001, . . . , 14096 by means of connecting arrays141, . . . , 144 and connection matrix 145, shown in block form in FIG.3. FIG. 4 depicts the actual arrangement of arrays 141, . . . , 144 andmatrix 145.

With reference to FIG. 4, array 141 (arrays 142, 143 and 144 aresubstantially the same as array 141) comprises three similar, butindependent busses 14121, 14122 and 14123. Each of these busses 14121,14122, 14123 implements, in the preferred embodiment, the GeneralPurpose Interface Bus (GPIB) protocol. This protocol is defined in IEEEStandard 488-1978 "Digital Interface for Programmable Instrumentation,"a well-known standard in the art of digital communication. Matrix 145,comprising forty-eight similar, but independent busses 145501, 145502, .. . , 145548, also utilizes the GPIB protocol. The interconnections ofthe various busses are arranged to provide modularity and fail-softoperation of DCN 140, as now explained.

The twelve tier 1 devices 1401, . . . , 1412 of FIG. 3 are partitionedinto groups of three devices-per-group. For instance, the first groupcontains devices 1401, 1402 and 1403. The circuit elements representingthese devices have been labeled `1`, `2`, and `3`, respectively, withinthe pictorial representation of each element. Thus, device 1401 has beendesignated with a `1`, device 1402 with a `2` and so forth. The numbersbelow `1`, `2` and `3` in each pictorial representation, that is, `0`,`1` and `2`, are indicative of the logical addresses to be associatedwith the actual element numbers. These logical designations will beutilized to describe information flow through DCN 140. With the aboveterminology, it is clear that the second group of devices containsdevices 1404, 1405 and 1406; these are actually the fourth (`4`), fifth(`5`) and sixth (`6`) devices having logical designations ` 0`, `1` and`2`. Any actual designations (A₁) can be converted to a logicaldesignation (L₁) via the relation L₁ =mod (A₁ -1, 3).

In the arrangement of FIG. 3, there are four groups of devices. Thedevices in each group serve as inputs to a corresponding connectingarray 141, . . . , or 144. For instance, devices 1401, 1402 and 1403 ofthe first group are associated with array 141. Each device in tier 1controls a unique means for transmitting information to and from itsassociated connecting array. For example, device 1401 controlstransmission means 14101, which typically implements the GPIB protocol.

Up to twelve tier 2 interfaces may be added per tier 1 group, and thismaximum is shown in FIG. 3. Since there are four groups and twelveinterfaces per group, a total of forty-eight interfaces are present inthe architecture of FIG. 3. These interfaces are designated 1421, 1422,. . . , 1468 and correspond to actual interfaces `1` through `48`,respectively. Actual interface designations (A₂) also have logicaldesignations (L₂) `0` through `11` determined by the relation L₂ =mod(A₂ -1, 12).

Each tier 2 interface has three input busses and generates anindependent output bus. For instance, interface 1421 is served by busses14104, 14105 and 14106 and controls bus 14501 on its output. Theprotocol on these busses is typically the GPIB. The input bussesoriginate from one of the connecting arrays 141, . . . , 144 and theoutput bus terminates on connection matrix 145.

With the above description, the interconnection provided by arrays 141,. . . , 144 may be described according to the following tables.

                  TABLE I                                                         ______________________________________                                        Array 141                                                                     Bus              Connects to busses                                           ______________________________________                                        14101            14104,14107,14110                                            14102            14105,14108,14111                                            14103            14106,14109,14112                                            ______________________________________                                    

                  TABLE II                                                        ______________________________________                                        Array 142                                                                     Bus              Connects to busses                                           ______________________________________                                        14201            14204,14207,14210                                            14202            14205,14208,14211                                            14203            14206,14209,14212                                            ______________________________________                                    

                  TABLE III                                                       ______________________________________                                        Array 143                                                                     Bus              Connects to busses                                           ______________________________________                                        14301            14304,14307,14310                                            14302            14305,14308,14311                                            14303            14306,14309,14312                                            ______________________________________                                    

                  TABLE IV                                                        ______________________________________                                        Array 144                                                                     Bus              Connects to busses                                           ______________________________________                                        14401            14404,14407,14410                                            14402            14405,14408,14411                                            14403            14406,14409,14412                                            ______________________________________                                    

The processing circuits 14001, . . . , 14096 of tier 3 are arranged tohave an equal association with all devices 1401, . . . , 1412 of tier 1.From one to eight tier 3 circuits are allowed per tier 2 interface; thearrangement of FIG. 3 shows the maximum limit. Consequently, the numberof tier 3 circuits that appear is ninety-six, and these circuits arelabeled `1` through `96` in the pictorial representations of circuits14001 through 14096. Corresponding to the actual designations (A₃) `1`through `96` are logical designations (L₃) `0` through `7` which may bederived from the relationship L₃ =mod (A₃ -1, 8). Also, each of theninety-six tier 3 circuits 14001 through 14096 controls eight contiguouslinks comprising outgoing data links 93001 through 93768 coupled toLTS's having actual designations `1` through `768` in FIG. 3. Each LTSwith an actual designation (A₄) of ` 1` through `768` has a logicaldesignation (L₄) determined by L₄ =mod (A₄ -1, 8).

FIG. 4 shows that circuits 14001 through 14096 are divided into twelvesets with each set containing eight circuits, and each circuit has fourinput busses and up to eight output data links. For instance, circuit14001 is served by input busses 145001 through 145004 originating frommatrix 145 and provides output links 93001 through 93008. All inputbusses 145001 through 145384 associated with circuits 14001 through14096 implement a parallel protocol, typically the GPIB, whereas outputlinks 93001 through 93768 are serial transmission links. The protocol onthe serial links will be discussed later.

The function of matrix 145 is to interconnect busses 14501 through 14548arriving at its input to busses 145001 through 145384 exiting itsoutput. The data bus means depicted as matrix 145 in FIG. 4 accomplishesthis function. Matrix 145 comprises forty-eight similar but independentbusses 145501 through 145548 implementing the GPIB protocol. On theinput side of matrix 145; incoming bus 14501 connects to internal bus145501; incoming bus 14502 connects to internal bus 145505; incoming bus14512 connects to internal bus 145545; incoming bus 145513 connects tointernal bus 145502; and so forth.

On the output side of matrix 145: internal bus 145501 connects tooutgoing busses 145004, 145008, . . . , 145032; internal bus 145502connects to outgoing busses 145003, 145007, . . . , 145031; internal bus145503 connects to outgoing busses 145002, 145006, . . . , 145030;internal bus 145505 connects to outgoing busses 145036, 145040, . . . ,145064; and so forth.

The interconnection arrangement of matrix 145 may be summarized with theaid of a shorthand notation, as follows: if interfaces 1421 through 1468are represented by the notation i(1), i(2), . . . , i(48), respectively,and the twelve sets comprising circuits 14001 through 14096 by m, m=1,2, . . . , 12, with m=1 corresponding to circuits 14001 through 14008,and so forth, then matrix 145 maps tier 2 interfaces and tier 3 circuitsaccording to the relation

    i(m+12(n-1)), n=1,2,3 and 4.

For example, with m=1, then interface devices i(1), i(13), i(25) andi(37), corresponding to actual devices 1421, 1433, 1445 and 1457, servethe set containing circuits 14001 through 14008.

2.1b Message Routing

With reference to FIG. 2, data links 920,921 arriving at the input toDCN 140 and outgoing data links 930,931 departing DCN 140 utilize aserial mode of transmission and a protocol that is bit oriented.Information is transmitted over these links in communication elementscalled frames. The bit pattern of a typical frame is shown in FIG. 5;this pattern is representative of conventional high level data linkcontrol type protocols. One example of a conventional link level(oftentimes designated Level II) protocol is the well-known synchronousdata link control (SDLC) protocol. With these protocols, the componentsof a frame include:

(1) an eight bit OPENING FLAG field to indicate the start of a frame;

(2) an eight bit ADDRESS field identifying the receiving station that iscontrolled by the transmitting station;

(3) an eight bit CONTROL field used by the transmitting station tocontrol the receiving station and by the latter station to respond tothe former station;

(4) a variable length INFORMATION field containing the message that isto be transmitted without constraints on length or bit patterns;

(5) a sixteen bit FRAME CHECK field to detect transmission errors; and

(6) an eight bit CLOSING FLAG field to indicate the end of a frame.

Of primary importance in the transmittal of messages within the MLTsystem is the data contained in the INFORMATION field. In general, MLTmessages have the format shown in FIG. 6. The message comprises a HEADERportion and a DATA portion. The HEADER includes a number of bytes toindicate: whether the message is a request or response (`request₋₋response`); routing procedure (`up₋₋ route` and `down₋₋ route`); theprocessor which is the source (`up₋₋ circuit₋₋ type`) and destination(`down₋₋ circuit₋₋ type`); the software task at the source (`up₋₋ task₋₋id`) and the destination (`down₋₋ task_(--id`)); and other bytes to bediscussed later. The DATA portion contains a variable number of bytesprimarily indicating the type of tests desired and the raw data measuredas a result of these tests. These DATA bytes will be discussed in detaillater.

Particularly pertinent to message routing in DCN 140 are the `down₋₋route` and `up₋₋ route` bytes. Whenever a message is sent from a FEcomputer 220 or 221 to a LTS 160 or 161, the `down₋₋ route` parameter,comprising two bytes, must be parsed in order to guide the messagethrough the three tiers of DCN 140.

As an example, it is supposed that a FE computer 220 or 221 is tointeract with an LTS that has an actual designation of `121` in FIG. 3.The actual decimal designation is decremented by one to yield a decimalvalue of 120 and this is represented in `down₋₋ route ` by the followingbit pattern:

    ______________________________________                                        bit    15      14     13    12   11    10   9    8                            position                                                                      value  0       0      0     0    0     0    0    0                            bit    7       6      5     4    3     2    1    0                            position                                                                      value  0       1      1     1    1     0    0    0.                           ______________________________________                                    

In general, bit positions 0, 1 and 2 are used by tier 3 circuits 14001through 14096 to decide which one of its eight associated outgoing datalinks 93001 through 93768 will be used to transmit the INFORMATION fieldto the appropriate LTS (`121` in this example). Bit positions 3, 4 and 5are used by tier 2 interfaces 1421 through 1468 to decide which one ofits eight associated tier 3 circuits 14001 through 14096 will receivethe INFORMATION field. Finally, bit positions 6, 7, 8 and 9 are used bytier 1 devices to decide which one of its twelve corresponding tier 2interfaces 1421 through 1468 will receive the INFORMATION field. In thisexample, parsing of the `down₋₋ route` two-byte parameter in conjunctionwith reference to FIGS. 3 and 4 indicates that:

(i) tier 1 device 1401, 1402, . . . or 1412 (say 1403) receiving theframe passes the INFORMATION field to the tier 2 interface havinglogical address (L₂) of `1` (binary 0001 is equivalent to decimal 1);

(ii) tier 2 interface 1422, corresponding to logical address `1`,receives the INFORMATION field and passes it to the tier 3 circuithaving logical address (L₃) of `7` (binary 111 is decimal 7); and

(iii) tier 3 circuit 14016, corresponding to logical address `7`, passesthe INFORMATION field, after reassembly into a data link protocol, tothe LTS having logical address (L₄) of `0` (000 in binary is decimal 0).

As indicated in FIG. 3, the LTS having logical address `0` at the outputof actual tier 3 circuit 14016 is the LTS labeled `121`, as requested.

Whenever any tier 1 device 1401 through 1412 receives a frame on itsdata link connection to FE computer 220 or 221, this is an indicationthat the INFORMATION field contained in the frame is to be propagated inthe so-called DOWN direction through the MLT architecture of FIG. 2. Theparameter in the HEADER portion of the INFORMATION field indicating theultimate destination is `down₋₋ circuit₋₋ type`, which will be discussedlater. The specific path through DCN 140 to this destination is found in`down₋₋ route`, as exemplified above.

A similar protocol is observed for messages traveling in the so-calledUP direction of the hierarchy. In UP transmissions, the pertinent HEADERparameters are `up₋₋ circuit₋₋ type` and `up₋₋ route`. As a message ispassed DOWN the hierarchy by DCN 140, appropriate return information issaved in `up₋₋ circuit₋₋ type` and assembled in `up₋₋ route` to allowfor an orderly progression UP the hierarchy. The bit positions of `up₋₋route` are interpreted as follows: (1) bits 4 and 5 are employed by tier1 devices to indicate the return path on one of two data linksassociated with each device 1401 through 1412; (2) bits 2 and 3 are usedby tier 2 interfaces 1421 through 1468 to return on one of three bussesconnecting each tier 2 interface to its associated connecting array 141,. . . or 144; (3) bits 1 and 0 are utilized by tier 3 circuits 14001through 14096 to return on one of four busses connecting each tier 3circuit to connection matrix 145.

In the example given above for routing in the DOWN direction, it issupposed, as above, that tier 1 device 1403 received the frame underconsideration on link 9206, as shown in FIG. 3. This link has logicaldesignation, `1`; in fact, the left-hand, incoming data link associatedwith each tier 1 device is the `1` link whereas the other link isdesignated `0`, by convention. Before routing the INFORMATION field totier 2 interfaces, the logical designation is converted to binary andbits 5 and 4 are filled with the binary representation--in this case 01.Tier 2 interface 1422 received the message on bus 14109 from array 141(FIG. 4); this bus is designated by a logical `0`; in fact, the threebusses entering a tier 2 interface from an array 141 through 144 arelabeled `0`, `1` and `2` starting with the right-most bus. Then, beforesending the message to tier 3 circuit 14016, bits 3 and 2 are given thevalues 0 and 0, respectively (`0` in decimal converts to 00 in two-bitbinary). Finally, since tier 3 circuit 14016 receives the message on itslogical `3` bus from matrix 145 (again, the right-most bus is logical`0` and the left-most bus in logical `3`), bit positions 1 and 0 arefilled with 1 and 1, respectively (`3` in decimal converts to 11 inbinary). To summarize for this example, the LTS having actual address A₄=121 receives a frame with the `up₋₋ route` parameter of HEADER filledas follows:

    ______________________________________                                        bit      7     6       5   4     3   2     1   0                              position                                                                      value    --    --      0   1     0   0     1    1.                            ______________________________________                                    

(Bit positions 6 and 7 generally have values but are not pertinent tothe immediate discussion and, therefore, have been shown withoutvalues).

As indicated in FIG. 3, each tier 1 device 1401, . . . , or 1412,receives two data links at its input. Since the typical MLT system isimplemented with twelve on-line FE computers, each FE computer 220 or221 supports two data links at its output. To provide a degree ofredundancy for fail-soft operation, FE computers 220,221 and tier 1devices 1401-1412 are interconnected so that there are two possiblepaths between each FE computer 220 or 221 and DCN 140. For example, FEcomputer 220 supports the two data links 9201 and 9219 that terminate ontier 1 divices 1401 and 1410, respectively. Similarly, FE computer 221implements two data links which terminate on devices 1412 and 1409. Withsuch a FE-to-DCN connection arrangement, if one of the FE-to-LTS pathscomprising the input data links 9201-9224 and DCN 140 fails during atransaction, it is possible to re-route the results from the given LTSto the appropriate FE computer over the alternate path. The folowingprocedure implements the the alternate routing technique.

Each FE computer 220,221 is initialized with a unique identifier. Thisidentifier is stored as part of the `logical₋₋ id` byte of the messageHEADER, as dipicted in FIG. 6, for all messages originated by theassociated FE computer. The `logical_(--id`) is not related to theactual physical connection to DCN 140. Thus, if a FE computer fails andis replaced by a backup computer, the backup inherits the identifier ofthe FE computer being replaced.

As a message travels DOWN the hierarchy, information about the returnpath is stored in `up₋₋ route`, as described above. When the messagereaches the designated one of the tier 3 circuits 14001-14096, thecompleted `up₋₋ route` byte and associated `logical₋₋ id` byte may beextracted. Each tier 3 circuit maintains a table containing the two mostrecently used upward paths for each `logical₋₋ id`. Since theinstruction routines controlling FE computers 220,221 generallydistribute information transmissions equally through DCN 140, the tablefor a given FE computer, at any one time, will contain `up₋₋ route`information on the two most recent paths needed to reach the particularFE computer in UP transmissions.

If an upward message connot reach the destination FE computer via its`up₋₋ route` information because of a primary path blockage, the messageis marked as failed and sent back to the originating Tier 3 circuit. Thetable entry for the same `logical₋₋ id` is accessed and the `up₋₋ route`information is replaced with the alternate or secondary `up₋₋ route`path. If any subsequent failures occur, the message is then discarded.

In some situations, it is possible that the two most recent entries inthe table do not correspond to the `up₋₋ route` byte in the UP message.This occurs in situations where long-term craft activities are inprogress, such as pair identification with an identifier tone providedby the MLT system. If a message fails to traverse the UP path on itsfirst attempt, then either path in the table may be used as an alternateroute.

2.1c Software Design

Each microprocessor executing within DCN 140 runs under supervision ofits own ROM-based operating system. However, each separate operatingsystem is identical, so only this one operating system, designated OS,requires explanation.

The OS provides a multitasking environment to that the operationsperformed by individual modules comprising the three-tiers of DCN 140can be partitioned into a series of suboperations called "tasks". Eachtask is dedicated to handling a specialized activity. The OS is arrangedto insure that the appropriate task gains control of its associatedmicroprocessor and commences execution of its programmed sequence when aparticular activity is requested. For example, one task resident in DCN140 is designed to handle GPIB activity; this task executes whenever abus transfer is required over any one of the numerous GPIB-type bussesembedded within DCN 140. Whenever a bus transfer is completed and noother transfers are required, the bus transfer task relinquishes controlof its microprocessor, and other scheduled tasks are now free to executeand satisfy requests for other activities. If no activities arescheduled, the OS is in its wait state, testing for a flag; a flag isset whenever a particular activity, and its associated task awaitexecution.

The microcomputer architecture, in pictorial form, for each tier of DCN140 is shown in FIGS. 7, 8 and 9 for tier 1, tier 2 and tier 3,respectively. There are, at most, six types of tasks implemented by anyparticular microcomputer within the hierarchy of DCN 140.

Five of these tasks are shown in FIG. 7, which depicts the architecturalarrangement for tier 1 device 1401 (the remaining tier 1 devices 1402through 1412 have essentially the same architectural arrangement asdevice 1401 and, therefore, device 1401 is taken as representative). Thetask designated SERIAL DATA within elements 11405 and 11406 of FIG. 7controls the activity associated with information transfer over serialdata links 9201 and 9202, respectively. This task (i) parses incomingframes (FIG. 5) received over a data link 9201 or 9202, extracts thecontents of the INFORMATION field, and stores the contents in a buffermemory within the controlling microprocessor that is accessible to othertasks; and (ii) performs the inverse to parsing on outgoing frames, thatis, constructs a frame for transmission by extracting the contents ofbuffer memory to form the INFORMATION field of the frame and augmentsthis field with the other fields (FIG. 5) needed for the serial protocolon links 9201 and 9202.

The task labeled PARALLEL OUTPUT within element 11407 controls thetransfer of information over parallel-oriented bus 14101 and, whenrequired, serves as the bus master. Information requiring transfer isextracted from or stored in buffer memory accessible by other tasks.

The ADMINISTRATION task, represented by element 11409, performs allnon-operational functions required in the local environment. Forinstance, ADMINISTRATION controls sanity and diagnostic testing and thereporting of trouble. With reference to FIG. 6, ADMINISTRATION utilizes`up₋₋ circuit₋₋ type`, `down₋₋ circuit₋₋ type`, `up₋₋ task₋₋ id` and`down₋₋ task₋₋ id` for communicating with other MLT microcomputers tosynchronize testing among the various modules.

The DUMP MEM task, represented by element 11411, waits a certain periodafter a reset or restart operation and determines if a snapshot of tier1 memory is to be sent to a FE computer 220 or 221.

The BROADCAST task, depicted by element 11412, replicates a message fortransmission in parallel to tasks having a plurality of appearanceswithin a particular tier or, in this case of tier 1, to SERIAL DATAtasks 11405 and 11406. Replication reduces throughput time by allowingseveral slow serial transfers to proceed in parallel.

Tasks are defined so that the programs executing in the microcomputersof DCN 140 are relatively independent of the hardware they control. Toaccomplish this, generally each hardware component having input oroutput (I/O) capability has both a hardware driver and a software bufferthat accompany the sole task controlling that I/O capability. Uponsystem initialization, a unique memory block is defined for each I/Ohardware component; this block is known only to the hardware drive andsoftware buffer associated with each I/O request. To service an I/Orequest, the buffer routine fills the appropriate memory block withcontrol parameters and signals the driver to start I/O processing. TheI/O operation is completed by the driver at interrupt level.

Whereas the only connection between the hardware driver and buffersoftware is the common memory block, the only connection between thedriver and the associated task is a flag or semaphore that is set by thedriver when its activity requires execution. The task awaits theoccurrence of the semaphore, after which the task is scheduled by OS. Inthis manner, a task never communicates directly with a hardware driver.

With reference to FIG. 7, the driver and software buffer functionsassociated with the incoming links 9201 and 9202 and outgoing bus 14101may be identified. For instance, INPUT DRIVER 11401 and INPUT BUFFER11403, interposed between incoming data link 9201 and SERIAL DATA task11405, perform the desired buffering on incoming link 9201. To transmita message between SERIAL DATA task 11405 and BUFFER 11403, the taskmakes a function call and passes appropriate parameters (e.g., thememory address of the assigned memory block and the address of thecompletion semaphore) to the function. The function that is called isreferred to as the buffer routine, and it is this routine that isrepresented pictorially by element 11403 in FIG. 7.

From FIG. 7 it may also be observed that INPUT BUFFER 11404 and INPUTDRIVER 11402 serve to interface SERIAL DATA task 11406 and incoming datalink 9202, whereas OUTPUT BUFFER 11408 and OUTPUT DRIVER 11410 servicePARALLEL OUTPUT task 11407 and parallel-oriented bus 14101.

The one task remaining to be defined is the PARALLEL INPUT taskrepresented by elements 11427, 11428 and 11429 in FIG. 8; this figurepictorially represents tier 2 interface 1421 (the remaining tier 2interfaces 1422 through 1468 have essentially the same architecturalarrangement as interface 1421 and, therefore, interface 1421 is taken asrepresentative). The PARALLEL INPUT task organizes message transfersacross the parallel-input busses 14104, 14105 and 14106 via theindividual tasks 11427, 11428 and 11429, respectively. These threePARALLEL INPUT tasks run under control of PARALLEL OUTPUT task 11407 ofFIG. 7, which is the bus master. INPUT DRIVER and INPUT BUFFER pairs11421,11424; 11422,11425; and 11423,11426 serve basically the samefunction as INPUT DRIVER and INPUT BUFFER pairs 11401,11403 (or11402,11404) of FIG. 7, that is, they indirectly couple PARALLEL INPUTtasks 11427, 11428 and 11429 to incoming parallel busses 14104, 14105and 14106, respectively. The primary difference lies in the parallel bitorientation of busses 14104, 14105 and 14106 as contrasted to the serialprotocol of links 9201 and 9202.

ADMINISTRATION task 11430, PARALLEL OUTPUT task 11431, DUMP MEM task11434 and BROADCAST task 11435 of FIG. 8 are the equivalent ofADMINISTRATION task 11409, PARALLEL OUTPUT task 11407, DUMP MEM task11411 and BROADCAST task 11412 of FIG. 7.

FIG. 9 depicts, in pictorial fashion, the architecture of tier 3 withinDCN 140. The four elements labeled 114009 through 114012 represent thePARALLEL INPUT task associated with incoming, parallel-oriented busses145001 through 145004, respectively. Each PARALLEL INPUT task performsin essentially the same manner as each PARALLEL INPUT task 11427, 11428or 11429 of FIG. 8. In addition, each PARALLEL INPUT task is indirectlycoupled to its associated hardware via an INPUT DRIVER and INPUT BUFFER,as depicted by element pairs 114001,114005; 114002,114006;114003,114007; and 114004,114008. These pairs operate basically the sameas INPUT DRIVER and INPUT BUFFER pairs 11421,11424; 11422,11425; and11423,11426 of FIG. 8.

The eight elements designated 114014 through 114021 represent the SERIALDATA task associated with outgoing, serially-oriented links 93001through 93008, respectivly. These eight tasks are equivalent to SERIALDATA task 11405 and 11406 of FIG. 7. Also, each SERIAL DATA task isbuffered from its associated hardware via an OUTPUT DRIVER and OUTPUTBUFFER, as depicted by the eight element pairs 114022,114030; . . . ;114029,114037. These eight element pairs are the counterpart to INPUTDRIVER and INPUT BUFFER pairs 11401,11403 and 11402,11404 of FIG. 7.

Finally, ADMINISTRATION task 114013, DUMP MEM task 114038 and BROADCASTtask 114039 of FIG. 9 serve to control tier 3 microcomputers in a mannerequivalent to tasks 11409, 11411 and 11412 of FIG. 7 or tasks 11430,11434 and 11435 of FIG. 8.

FIGS. 7, 8 and 9 are pictorial in the sense that they indicate a logicalsituation in terms of the number of copies of software utilized toimplement the tasks. For example, the tier 3 architecture of FIG. 9indicates there are four distinct PARALLEL INPUT tasks 114009 through114012 and eight distinct SERIAL DATA tasks 114014 through 114021.Actually, there is only one copy of the PARALLEL INPUT program and onecopy of the SERIAL DATA program stored in microcomputer 14001. There arefour distinct read/write (R/W) memory regions or stacks dedicated toPARALLEL INPUT tasks and eight distinct R/W stacks dedicated to SERIALDATA tasks. The state of each task is kept in the appropriate stack. TheOS retains parameters indicating where, within each stack, the taskshould commence execution of an activity request.

The environment described immediately above basically defines theconcept of a multitasking operating system. In terms related to tier 3interfaces, multitasking obtains because four independent PARALLEL INPUTprograms are executed from within four distincts environments by thecentral processing unit of each microcomputer, namely, the four PARALLELINPUT tasks 114009 through 114012. Similar remarks apply to the eightSERIAL DATA tasks 114014 through 114021 of FIG. 9.

2.1d Software Operation

To understand how each of the microcomputers embedded in DCN 140operates in terms of an unfolding sequence in time, processing circuit1401 of FIG. 7 is considered as exemplary. As previously discussed,there are six application tasks and their interaction with the OS toconsider. However, the concepts may be readily conveyed by presentingthe interaction of a subset of these tasks, namely, SERIAL DATA,PARALLEL OUTPUT and ADMINISTRATION, as now discussed. At system startup,the OS commences execution by: (i) initializing its associated internalrandom-access memory; (ii) organizing memory blocks to serve as messagebuffers and placing these buffer locations onto a list called the FREEbuffer list; (iii) scheduling each task to run according to apreselected priority; and (iv) shifting execution to the SCHEDULERprogram. Since the only tasks that have been scheduled to this point inthe execution are those arranged in preselected order, the SCHEDULERfinds that the first task, designated Task 0, is READY to RUN. Task 0controls the incoming data link having logical designation `0`, so withreference to FIG. 7, Task 0 is identified as SERIAL DATA task 11405 andits associated data link is line 9201.

Just prior to transferring execution to Task 0, the SCHEDULER identifiedthe stack to be associated with Task 0. Once the stack location isidentified, execution of Task 0 commences from the first programstatement. Since Task 0 controls a serial data link (link 9201 havinglogical designation `0` in FIG. 7), the task begins by making a systemcall to OS to obtain an unused message buffer from the FREE list ofbuffers and then sets up data link INPUT BUFFER 0 program (element 11403of FIG. 7) to receive data into the now allocated buffer. Task 0 theninitializes link 9201 by arranging and sending a data link start-upmessage. Task 0 finally relinquishes control of the central processingunit (CPU) of its associated microcomputer by making a system call toOS.

The OS SCHEDULER program is entered again and, since the initializationprogram of OS has made all tasks READY to RUN, Task 1, having the nexthighest priority, is READY to RUN. The CPU is arranged to execute in thestack environment of Task 1, and control is then passed to Task 1. Task1 begins to execute from the first statement in its program.

Since Task 1 controls data link `1`, (link 9202 in FIG. 7), it executesessentially the same program as did Task 0, the only difference beingthat the stack areas in memory have different locations. A view of thestack associated with Task 0 at this point in the execution of Task 1indicates a wait state in which data link 9201 is set up to receive dataand a data link start-up message has been transmitted. In contrast, thestack of Task 1 indicates that link 9202 is quiescent. However, uponrelinquishment of the CPU by Task 1, its associated stack is also primedin the wait state.

The SCHEDULER program finds Task 2 READY to RUN. This task is the onedepicted as PARALLEL OUTPUT task 11407 of FIG. 7 and controlsparallel-oriented bus 14101. Basically the same program sequencingoccurs in Task 2 as in the prior task executions. The CPU is arranged tooperate in the stack environment of Task 2, and begins by executing fromthe first statement in the so-called GPIB program since bus 14101 ispresumed to implement the GPIB protocol. A message buffer is obtainedfrom the OS, and the OUTPUT DRIVER-OUTPUT BUFFER interface is arrangedfor message transmission or reception. Task 2 then relinquishes controlof the CPU.

Since Task 3 is READY to RUN, the SCHEDULER program sets up the CPU toexecute in the stack environment of Task 3. In FIG. 7, Task 3 may beidentified with ADMINISTRATION task 11407. The instructions of Task 3call OS to arrange for OS to schedule an execution of the so-calledADMIN program only when certain events occur. Task 3 also arranges for atimeout of about 15 seconds to schedule the ADMIN program for execution.ADMIN resets a timer whenever timeout occurs. If this timer signal isnot reset in this manner, the tier 1 device 1401 is considered to havelost its sanity and a RESET of the microcomputer occurs upon expirationof the timer interval.

As suggested above, the task numbers indicate the order of priority inexecution, with Task 0 having the highest priority and Task 3 thelowest. The execution of tasks in the sequence described above presumesno external event interrupted the progression through task executions,and the time diagram in the top half of FIG. 10 depicts such a sequence.It is possible, however, to have an external event interrupt thetop-down sequencing. For instance, if data link 9201 had a message tosend in the DOWN direction prior to the execution of Task 3, then Task 0would execute before Task 3 even executed for the first time.

As an example demonstrating external event interrupts and one that isexemplary of the typical operation of a tier 1 device, it is supposedthat the four tasks discussed in the above example have RUN and the OSis in the state of awaiting the posting of a flag to indicate a task isREADY to RUN (i.e., the rightmost state in the top diagram of FIG. 10).It is further supposed a message is now received over data link 9201 fortransmission to LTS 161 (FIG. 3). With reference to the bottom timediagram of FIG. 10 and the numerals associate with the various periodsof execution of the individual tasks, the following sequencing occurs:

(1) A message is received over data link 9201 or `0`, and INPUT DRIVER11401 signals OS that Task 0 should execute.

(2) Task 0 begins to execute to verify the message via the high levelprotocol acceptance technique.

(3) At interrupt level, a message is received across bus 14101. Task 2is made READY to RUN, but execution is precluded until Task 0relinquishes control of the CPU. The message on bus 14101 is headed UPthe hierarchy, say over link 9202.

(4) At the completion of the verification phase and message reception byTask 0, the message is sent to Task 2 since the `down₋₋ circuit₋₋ type`field in the HEADER indicated a LTS was the ultimate messagedestination. During this interval, the OS SCHEDULER begins execution.Now Task 2 has the highest priority that is in the READY to RUN state,and control is passed to Task 2.

(5) Task 2 processes the message sent to it by Task 0, and beginssending output over GPIB bus 14101 to the tier 2 interface indicated inthe `down₋₋ route` field of HEADER. Now the message previously receivedfor UP direction transmission may be processed by Task 2 beforerelinquishing control of the CPU. A signal is sent so that Task 1 may bemade READY to RUN, and control is passed to OS.

(6) the SCHEDULER sees that Task 1 is the highest priority task that isREADY to RUN, and passes control to Task 1.

(7) Task 1 processes the message available through Task 2 and sends themessage, properly formatted, over data link 9202. Control is passed backto OS.

(8) The output previously initiated over bus 14101 is now completed soTask 2 is made READY to RUN and OS passes control to Task 2.

(9) Task 2 effects follow-up processing by freeing the message bufferfor use elsewhere by the microcomputer and relinquishes control of theCPU.

(10) No task is presently READY to RUN until the interrupt handler fordata link `1`, via INPUT DRIVER 11401, signals OS that transmission UPlink `1` is now complete, whereupon Task 1 should be executed. Controlis passed to Task 1.

(11) Task 1 performs clean-up operations for its recent transmissionover data link `1`. OS is again given control.

(12) The SCHEDULER continues to execute until another I/O activity inthe microcomputer indicates that a particular task should RUN.

By way of a shorthand notation, which is similar to the actualhigh-level language utilized to program the tasks, the routingalgorithms realized in device 1401 may be summarized as follows:

    ______________________________________                                        (i)      Routing Algorithm for Task 0 and Task 1:                                      if (`down -circuit -type` = DCN -1){                                          pass message to local ADMINISTRATION                                          task;                                                                         }                                                                             else { destination = bits 6, 7, 8 and 9                                       of `down -route`;                                                             set `up -route` bits 4 and 5;                                                 pass message to PARALLEL OUTPUT                                               task;                                                                         }                                                                    (ii)     Routing Algorithm for Task 2:                                                 if (`up -circuit -type` = DCN -1){                                            pass message to local ADMINISTRATION                                          task;                                                                         }                                                                             else { if (`up -route` bits 4, 5 = 00 }                                       pass message to SERIAL DATA 0;                                                }                                                                             else { pass message to SERIAL                                                 DATA 1;                                                                       }                                                                    ______________________________________                                    

In each of these routing algorithms, the symbolic notation DCN₋₋ 1 hasbeen utilized. As alluded to earlier in this section, generators ofmessages can indicate not only the destination (`down₋₋ route` and `up₋₋route`) but also the microcomputer type within the hierarchy of the MLTsystem. DCN₋₋ 1 is one type and refers to tier 1 devices of DCN 140.Other types that may be referenced in bytes `down₋₋ circuit₋₋ type` or`up₋₋ circuit₋₋ type` include: MLT₋₋ CNTLER for FE computer 220 or 221;DCN₋₋ 2 for tier 2 interfaces and DCN₋₋ 3 for tier 3 circuits of DCN140; LTS₋₋ CNTLER for the LTS controller, PORT₋₋ CNTLER for portcontroller and PMU₋₋ CNTLER for precision measurement unit controller;these latter three controllers are found in LTS 160 or 161.

As indicated in Section 2.1a with reference to FIG. 4, the bussesserving as inputs to and outputs from connecting arrays 141-144, as wellas the array busses themselves, implement the GPIB protocol. Similarly,the input and output busses associated with matrix 145 utilize the GPIBprotocol. In the case of an array 141, . . . , or 144, it is evidentfrom FIG. 4 that each tier 1 device controls an output GPIB bus that hastwelve talker/listeners. For instance, bus 14101 is controlled by tier 1device 1401 and the twelve T/L networks on bus 14101 serve as inputs tointerfaces 1421-1432, respectively. Within this GPIB framework, it isnecessary to provide an embedded protocol for connecting a plurality ofT/L networks to a controller on the same GPIB bis so that messages maybe transmitted efficiently and message overhead is mitigated in returnof message accept/reject status information. The particular PARALLELOUTPUT task and the associated PARALLEL INPUT task accomplished theembedded protocol. Further discussion of this second-level protocol isheld in abeyance until GPIB circuitry and software are presented.

2.2 Loop Testing System (LTS)

2.2a Structure

Referring again to FIG. 2, it is shown pictorially that wire-centerbased LTS 160 (LTS 161 is substantially the same) performscommunication, loop access and loop testing functions. LTS 160 isactually an arrangement of loosely coupled microprocessors organized toperform these functions. The term "loosely coupled" is used herein todenote an organization of processors that share to common memory butcommunicate by passing messages over serial or parallel orientedchannels.

FIG. 11 shows a block diagram of LTS 160. LTS controller 2000 isresponsible for communications with DCN 140 (FIG. 2), via serial datalink 930, and for local control of other LTS subcomponents, including:precision measurement unit (PMU) 2101, 2102 and 2103; port controller2200; talk circuits 2301 through 2306; direct distance dialer (DDD)circuit 2400; ringing distributor 2500; and portions of equipment accessnetwork (EAN) 2700. Each of these subcomponents is explained as thediscussion proceeds.

LTS controller 2000 and port controller 2200 are linked withinterconnect bus 20001, which typically supports a parallel-orientedprotocol such as the GPIB. Port controller 2200 is responsible for theloop access function in that it provides tip, ring and sleeve controlfor connections to so-called "no-test" trunks 940 that enable the MLTsystem to interface to switching machine 170 (FIG. 2). A no-test trunkis one that provides the ability to interconnect to any customer line180 or 181 in a bridging mode. One such test trunk is shown as TIP1--RING 1 pair 9401 with its corresponding sleeve lead S1 lead 9417 inFIG. 11.

PMU's 2101 through 2103 are also interconnected to LTS controller withbus 20001. Each PMU 2101, 2102 or 2103 is a general purpose testingcircuit that is used to make measurements on customer loops 180 and 181.Each LTS 160 may contain from one to three PMUs. The maximum number isdepicted in FIG. 11. PMU 2101 (PMU 2102 or 2103 is similar) accesses acustomer loop 180 or 181 through a serial arrangement comprising, forexample: wire pair 21010 emanating from PMU 2101; equipment accessnetwork 2700; wire pair 28010 serving as the input to port device 2801;and port device 2801, which is an interface to no-test trunk pair 9401.EAN 2700 serves to interconnect any PMU 2101, 2102 or 2103 to any portdevice 2801, . . . or 2816 under control of both LTS controller 2000,via bus 20002, and port controller 2200, via bus 22001. The L CONTROL2701 portion of EAN 2700 connects to bus 20002, whereas the P CONTROL2702 portion of EAN 2700 connects to bus 22001.

LTS controller 2000, port controller 2200 and PMUs 2101 through 2103 areeach self-contained microprocessor modules. Because of the relativeindependence of these microprocessor modules, the MLT system is modularso that wire centers (150 or 151 of FIG. 2) ranging from one thousand toone hundred thousand customer loops can be served by augmenting thebasic system. Thus, as a wire center grows, more PMUs can be added (upto three per LTS), up to sixteen port circuits can be accommodated (themaximum of sixteen is shown in FIG. 11 as circuits 2801 through 2816),and EAN 2700 can be expanded. Hence the largest size LTS can have up tosixteen loops simultaneously accessed for testing and can time sharethree identical PMUs to perform requested tests. The separation of thetesting function, access function and communication function allows forthe simultaneous operation of these functions, thereby maximizingthroughput for a given testing traffic load.

2.2b LTS Operation

With reference to FIG. 11, LTS controller 2000 implements aserial-oriented protocol function on incoming data link 930. Receivedmessages, in the form shown in FIG. 5, are parsed to obtain theINFORMATION field as shown in FIG. 6, and then interpreted in LTScontroller 2000. An access request is typically the first messagereceived, as indicated in the `down₋₋ task₋₋ id` byte of the HEADER bythe binary equivalent of ACCESS and in the `request₋₋ response` byte asREQUEST in binary representation. This message causes LTS controller2000 to initialize an area of its RAM to track and time the request aswell as to generate a parallel-protocol message for passage over bus20001 to port controller 2200. The information utilized to constructthis latter message is found in the DATA portion of the INFORMATIONfield of FIG. 6. For instance, the first byte (byte 1) may be,symbolically, `ACC₋₋ NOTEST`. This indicates that the type of accessdesired is a connection to a "no-test" trunk. Another byte wouldindicate the `switch₋₋ type` to inform port controller 2200 of the typeof switching machine (e.g., an electronic central office or a cross-baroffice). The next several bytes list the telephone number of thecustomer loop to be accessed. Based on message content, port controller2200 proceeds to access the loop specified in the message by attachingtrunk dialer 2650 (see FIG. 11) to a free port 2801 through 2816,dialing the telephone number, and attaching busy/speech detector 2600 todetermine whether the loop is idle.

Presuming loop access is obtained, port controller 2200 sends a responseacross GPIB 20001. This response proceeds in the UP direction and,accordingly, appropriate INFORMATION field bytes must be filled. Withreference to FIG. 6, the `request₋₋ response` byte has the entryRESPONSE in binary form placed in the HEADER. In the DATA portion, byte1 has en entry that echos the test code which, in this case, is `ACC₋₋NOTEST`. This is to indicate that the completed request conforms to thedesired request. The second byte (byte 2) indicates the `status` of therequest and the third byte (byte 3) indicates the `port₋₋ number`. Forthe instant example, these bytes might read, symbolically as `ACC₋₋COMPLETE` and `PORT₋₋ 1` to indicate that port 2801 of FIG. 11 has aconnection established to the loop associated with the telephone numbersent in the DOWN direction.

At this point in the operation, the loop is accessed, and LTS 160 awaitssubsequent requests, typically to effect testing. Most test requestsrequire the services of one PMU 2101, 2102 or 2103. However, somerequests can be satisfied by either LTS controller 2000 or portcontroller 2200 and their associated circuitry. Test requests are codedso that LTS controller 2000 can determine which LTS circuits can satisfythe request. LTS controller 2000 therefore acts as a resource managerfor the entire LTS 160.

In order to proceed with the operational description of LTS 160, it isnecessary to discuss its component parts in some detail. Attention isfocussed first on LTS controller 2000, followed by port controller 2200and PMU 2101 and, finally, the remaining circuitry of LTS 160 shown inFIG. 11.

2.2.1 LTS Controller

LTS controller 2000 is a microcomputer-based system also running underthe same operating system (OS) as DCN 140. Again, the softwarecontrolling the microcomputer is partitioned into tasks, and taskscommunicate with each other by signaling each other or by sendingmessages to one another via facilitates provided by OS. In LTScontroller 2000, the tasks are as follows:

(a) SERIAL DATA task controls data link 930 and implements a high leveldata link protocol on all messages passing onto or coming from physicaldata link 930. All tasks that must transmit data over link 930 do so bysending the data as a message to the SERIAL DATA task. This task isequivalent to the SERIAL DATA task 114014 of FIG. 9 associated with DCN140. All messages entering LTS 160 and destined for a specific task inLTS controller 2000 must pass through SERIAL DATA.

(b) PARALLEL DATA task controls the transmission and reception ofmessages over parallel-oriented bus 20001 shown in FIG. 11. All tasksthat must transmit data over bus 20001 to port controller 2200 or thePMU's 2101-2103 do so by sending the data as a message to the PARALLELDATA task. Similarly, data received from controller 2200 or units2101-2103 pass through the PARALLEL DATA task. This task is equivalentto the PARALLEL OUTPUT task 11407 of FIG. 7 associated with DCN 140.

(c) ACC task processes requests for access to trunks 9401 through 9416of FIG. 11 and requests for establishment of callback paths via thenational direct distance dialing (DDD) network as implemented by DDDcircuit 2400. The processing of requests for loop access includes theformatting of messages to port controller 2200, where the access isactually performed, and the setting up of a timeout over the accessactivity in port controller 2200. The ACC task indirectly sends amessage for loop access to port controller 2200 by sending the messageto the PARALLEL DATA task. Requests to DDD circuit 2400 are transmittedover bus 20002.

(d) TST task controls the processing of test requests on a given port,selected from one of the ports 2801 through 2816, once that port hasaccessed a loop for testing. There are sixteen TST tasks, one for eachpossible port 2801, . . . , 2816. The TST tasks are not bound to aparticular port number in a fixed manner, but may be assigned to anyindividual port 2801-2816 over a long period of time. For example, forthe duration of a given loop access, TST 7 task may be assigned to port2803. When the access to port 2803 is dropped, TST 7 task may beassigned to port 2801. Once the assignment is made, it is fixed for theduration of the loop access. This dynamic assignment allows processingpriority to be evenly distributed among ports 2801-2816. TST tasksoftware either performs the test request itself or arranges for thetest to be performed by either port controller 2200 or PMU's 2101-2103.TST task also provides a timeout function for the request.

(e) TCD task controls the dialing for talk circuits 2301-2306. This taskcan manipulate DDD circuit 2400 and thereby arrange a callback to,typically, a craftsperson at the facility designated the MaintenanceCenter which contains the I/O terminals 230,231. The callback feature isrequired to implement the combined talk/test procedures of the MLTsystem whereby a craftsperson can be in speech communication with eithera customer or another craftsperson over a loop accessed for testing. Themaintenance administrator at the Maintenance Center can enter a testrequest as a MLT system user, have that test run by LTS 160 while thetalk path is broken, and when the test is completed, have the talk pathrestored by LTS l160. These are two TCD tasks in LTS controller 2000software so that two dialing operations may be concurrently in progress.

(f) ADMINISTRATION task provides all administrative functions in LTS2000. These functions include: sending to FE computer 220 or 221 arequest for data base download when LTS 160 is reset and processing thisdownloaded data base; responding to echo messages from ADMINISTRATIONtask of DCN 140; and providing an interface during self-diagnosticchecking.

(g) DIAGNOSTICS task provides self-testing capabilities that are used todiagnose LTS controller 2000 hardware problems. DIAGNOSTICS taskinterfaces to ADMINISTRATION task, via the OS message passing facility,to request and receive the reservation of LTS 160 hardware for use inconducting self-tests.

(h) DUMP MEM task arranges for the transmission of a snapshot of LTScontroller 2000 memory when a malfunction occurs.

At system startup or when a system reset occurs, operating system OSinitializes its tables, places all message buffers on "free queue" ofbuffers, initializes all system semaphores or inter-task signals, andmakes each task READY to execute (RUN). The OS then calls a hardware andsoftware initialization function. Tables are kept in permanent memoryand define the state of the equipment configuration to be associatedwith the particular LTS 160. For instance, the number of PMU's 2101-2103configuring the particular MLT system is one such table parameter. Thesetables are accessed for initialization. Next, the task schedulingfunction, again called the SCHEDULER, is executed. Program execution inLTS 160 is similar to that of the DCN 140 once the SCHEDULER is called.Thus, execution is transferred from the SCHEDULER to the highestpriority task which is READY to RUN. At startup, all tasks are READY,and the SERIAL DATA task has the highest priority. Execution of SERIALDATA enables the hardware receiver associated with link 930 and causes atransmission of a data link start-up message to DCN 140 in the highlevel protocol format. The SERIAL DATA task then relinguishes control ofthe CPU in LTS controller 2000. The OS is now free to select anothertask for execution.

The PARALLEL DATA task has the next highest priority and executes so asto enable its associated hardware for two-way communication on bus20001. Control is again passed to the OS once the task is initialized.

All the other tasks eventually RUN and initialize themselves and theirassociated hardware. The tasks then await some activity requiring theirspecialized services. Usually they wait to receive a message buffer orfor a semaphore to be posted. It may also be that a particular task iswaiting for a timeout to occur before regaining control of the CPU. Forexample, ADMINISTRATION waits for about seven seconds before gainingcontrol after its initialization; this task then sends a data basedownload request to FE computer 220 or 221 by passing the message toSERIAL DATA for transmission over data link 930.

The download data messages from FE computer 220 or 221 pass through theSERIAL DATAL task and are routed accordingly to data in the INFORMATIONfield. Download messages have LTS₋₋ CNTLER (LTS controller) names in`down₋₋ circuit₋₋ type` byte and ADMINISTRATION task in the `down₋₋task₋₋ id` byte. Consequently, the routing function in LTS controller2000 realizes that the INFORMATION field is to be processed in LTScontroller 2000 itself and sends the message, via OS, to ADMINISTRATIONtask. This task processes the message by passing the data that appearsin the DATA portion of the message. Download messages identify thenumber of equipment types installed at the particular LTS 160 site andthe present status of the equipment (AVAILABLE, OUT₋₋ OF₋₋ SERVICE, andso forth). These messages also organize ports 2801-2816 into trunkgroups, specify dialer types associated with talk circuit 2301-2306, andso on. After configuration information has been downloaded, LTS 160 isprepared to process access and test requests.

2.2.1a Access Request Processing

Access request messages have LTS controller 2000 specified in the`down₋₋ circuit₋₋ type` of the message header symbolically as LTS₋₋CNTLER and the ACC task in the `down₋₋ task₋₋ id` symbolically as ACC.The SERIAL DATA task routing function transmits the access message tothe ACC task.

The format of the DATA portion of the INFORMATION field of FIG. 6 hastwo possible arrangements depending on the type of access desired. Fourtypes of access are allowed:

(i) a regular test access of customer loop 180, . . . , 183; theINFORMATION field is exemplified in FIG. 12;

(ii) a main distribution frame (MDF) trunk access as also exemplified byFIG. 12;

(iii) a regular test access plus a callback to the Maintenance Center;the INFORMATION field is exemplified in FIG. 13; and

(iv) a callback of the Maintenance Center that is to be associated witha specified test access already in effect at LTS 160 site; FIG. 13 alsodepicts the corresponding INFORMATION field.

Processing for each of these types of access is covered next.

2.2.1a.1 Regular Test Access and MDF Trunk Access

Regular test access requires that circuitry and equipment withinswitching machine 170 be manipulated according to the type of centraloffice (e.g, cross-bar or electronic). MDF trunk access requires onlythat local memory tables be updated with entries disclosing, in effect,that the trunk circuit is being attended to by craft personnel. MDFtrunks are not automatically connected to a customer loop, but requireinteraction and manipulation by a craftsperson located at the MDF.

The ACC task begins to RUN when a message is sent to it. In theimmediate case, the message is a REQUEST for either a test trunk or MDFtrunk access. A memory table is used to store pertinent informationabout the REQUEST; such information includes the address of the REQUESTmessage, memory locations for the storage of the address of a RESPONSEmessage, and whether a callback is required for this REQUEST. The accesscode (regular, designated by NOTEST access, or MDF access), theswitching machine type, the trunk group containing the loop under testand the telephone number of the customer are placed as data in themessage buffer. The address of the original REQUEST message and theaddress of the table used to store information about the REQUEST arealso placed in the message HEADER, in the `up₋₋ 1parameter` and `up₋₋2parameter` locations, so that the response of port controller 2200 canbe identified with the present REQUEST. The message is then sent toPARALLEL DATA task for transmission to port controller 2200. A timeoutis started on the activity of port controller 2200 and ACC taskrelinguishes control of the CPU.

When port controller 2200 completes its processing of the accessrequest, it returns a RESPONSE message to ACC task by sending themessage across the PARALLEL DATA task. ACC task is identified in the`up₋₋ route` of the message HEADER and the routing function in PARALLELDATA task sends the message to ACC task. ACC task associates theRESPONSE message with the original request message by checking for theaddress of the original request message and of the temporary storagetable used for the request. Th access response message has the formatshown in FIG. 14. The `status` byte indicates whether the access wassuccessful or not. If it was unsuccessful or if LTS controller 2000 hadtimed out on port controller 2200 request, a RESPONSE message is formedand sent to SERIAL DATA task for transmission UP the hierarchy. Thetemporary table used to store data for the failed request is now madeavailable for use with another access REQUEST that may have arrived.

If port controller 2200 passes a RESPONSE that indicates an access hasbeen obtained, ACC task attempts to close a relay embedded withinequipment access network (EAN) 2700 (FIG. 11) to one of the ports2801-2816 selected for loop access. If this operation fails, troublecounters are stroked against the selected port 2801-2816 and EAN 2700and the aforementioned failure sequence is followed again. If relayclosure is successful, ACC task selects an idle TST task to controltesting on the selected port, arranges to have a memory space called theport control table filled with information about the access, and makesthe chosen TST task READY to execute. Port control table informationincludes the address of the original request message, the address of theresults buffer received from port controller 2200, whether the access isof long or short holding time, a timeout value to be used to timeout theaccess before it is automatically dropped, the logical identifier of theFE computer that requested the access, and an identifier that allows theFE computer to associate the access with a results buffer internal tothe FE computer. ACC task is now finished with its processing of thisaccess request, and makes its temporary table available for use with anew access request. The return of a RESPONSE message is theresponsibility of the TST task, and will be covered in a later section.This convention has been adopted because the original REQUEST messagemay have a test REQUEST appended to the access REQUEST.

2.2.1a.2 Interactive Access Request Processing

The interactive access request message of FIG. 13 is used when a loopaccess is desired together with a talk path to a craftsperson in theMaintenance Center. The request messsage format is basically the sameone used for a regular test access, as per FIG. 12, except that acallback telephone information has been appended and the `request₋₋code` is symbolically designated ACC₋₋ INTR (as contrasted to ACC₋₋NOTEST or ACC₋₋ MDF of FIG. 12). The ACC task processes the so-called"regular loop portion" of the message as outlined above. However,besides formatting and sending a message to port controller 2200, amessage is also sent to one of the TCD tasks. This latter messagecontains the callback telephone number appearing in the original DOWNroute REQUEST message as is shown in FIG. 15. The ACC task now waits toreceive two RESPONSE messages, nanely, one from port controller 2200 andone internally from TCD task. A timeout is started on these activities.

The TCD task starts to RUN as soon as it can be scheduled after ACC taskrelinguishes control of the CPU. TCD task receives messages sent to itand begins to execute its dialing algorithm. The task also attempts toacquire one of talk circuits 2301-2306. If no circuit 2301-2306 isavailable, the callback sequence fails and a message to this effect issent to ACC task. If one of the circuits 2301-2306 is available, TCDtask attempts to acquire either a dial pulse dialer or in-band dialerfor use with the available talk circuit. Th dialer is represented inFIG. 11 by DDD circuit 2400. The dialer type depends on the centraloffice equipment used to terminate the talk circuit, which appears tothe central office switching machine as a station set on a customerloop. The dialer type is a parameter contained in the download data sentfrom the FE computer to LTS 160 as part of the startup sequencediscussed above. If there is no dialer circuit 2400 available, eitherbecause it is presently in use or out of service, the callback sequenceis terminated, the selected talk circuit is released and made availablefor use on another callback request, and a failure message is sent toACC task.

If dialer circuit 2400 is acquired, the callback digits D1, D2, . . . ,D12 are passed to a dialing program, and the digits are dialed. Thedialing occurs at the interrupt level since dialing takes between 1 and10 seconds to complete and, consequently, TCD task gives up control ofthe CPU for the dialing interval at least. When dialing is complete, aninterrupt handler posts a semaphore to signal TCD task that it shouldreturn and continue its processing. Before having relinguished controlof the CPU, TCD task started a timeout on the dialing activity. If thistimeout expires before notification of dial completion, TCD taskarranges to free its associated equipment, namely, one of the talkcircuits 2301-2306 and dialer 2400, and generates a failure message forACC task.

If dialing successfully completes, TCD task frees dialer 2400 circuitry,and enables the allocated talk circuit 2301-2306 for the detection of ahandshake signal called "KEY-ZERO". The craftsperson at the MaintenanceCenter is required to depress the "0" key on the in-band signaling padof the telephone set to signal LTS 160 that the callback has beensuccessfully received at the Maintenance Center. The TCD task starts atimeout for the reception of the KEY-ZERO signal by the talk circuithardware, and if the timeout expires before the signal is received, thecallback is aborted, and the failure procedure outlined above isinitiated. If the KEY-ZERO signal is detected by the talk circuit, thecallback sequence is completed, and an indication of this is formattedand returned to ACC task. The message contains information identifyingthe talk circuit 2301, . . . , or 2306 utilized.

The ACC task can receive RESPONSE messages from TCD task and portcontroller 2200 in either order since the activities of callback andloop access are asynchronous with respect to each other. After bothresponses arrive, ACC task completes its processing of the accessrequest by checking `status` results and either sending to message to FEcomputer 220,221 or by connecting the allocated port from ports2801-2816 and the selected talk circuit from circuits 2301-2306 throughEAN 2700. If the loop access failed, or if the attempt to connect theallocated port fails, a failure message is returned to the correspondingFE computer, and LTS 160 equipment on the failed arrangement isrelinguished. If the connect attempt fails for the allocated talkcircuit, the talk circuit equipment is freed, trouble counters arestrobed, and a TST task is selected for loop access in the mannerdescribed above. If the callback attempt is successful, the loop accessis successful, and the connection through EAN 2700 is successful, a TSTtask is selected to oversee testing on the loop, and ACC task completesits processing with basically the same procedure as described above forthe "loop access only" case.

2.2.1a.3 Callback Access Processing

There are instances when a Maintenance Center administrator needs totalk to either a customer or to an outside repair person after thecustomer loop has been successfully accessed for testing. In theseinstances, LTS 160 receives basically the same message of FIG. 13 exceptthat the `request₋₋ code` is, symbolically, ACC₋₋ DDD and the port2801-2816 to be associated with the callback in the `down₋₋ parameter`byte of the HEADER.

The ACC task begins to execute when this message is received. It formatsa message for TCD task as outlined above for the interactive test case,sends the message and waits for a RESPONSE. A timeout is started to timethe callback request. The TCD task processes this message exactly asdescribed above, and returns its response to ACC task. No message fromport controller 2200 is expected in this case, so ACC task proceeds tosend a message to the FE computer associated with the ACCESS request orto attach one of talk circuits 2301-2306 to the specified port,depending on the `status` returned from the callback activity.

The description to this point in this section has covered in some detailthe action of ACC task and TCD task. It should be recalled that thesesoftware functions operate in a multitasking environment, and that atany instant, ACC task can be processing several access requests that arein different states of completion. However, TCD task is designed toprocess one dialing request at a time. To insure efficient throughput,there are two TCD tasks within the software of each LTS controller 2000.Consequently, two dialing activities can be going on in LTS controller2000 concurrently. Since there are two dialer types, namely, dial pulseand an in-band, in LTS 160 for dialing over the national telephonenetwork, two TCD tasks insures that maximum dialing activity may occur.

2.2.1b Test Request Processing

An active TST task has a private memory table that it uses to controltesting on a given port. Entries in this table include the address for arequest message or addresses for a series of messages and thecorresponding address or addresses for the responses. TST task is firstactivated by the action of ACC task, which attaches both a requestbuffer and a response buffer to the table. Then TST task begins atimeout of the loop access; if the timeout expires before the loopaccess is dropped by request, the loop access is automatically droppedby LTS controller 2000. This timeout prevents the loss of use of LTS 160circuitry such as talk circuits 2301-2306 and ports 2801-2816 in caseswhere FE computer 220 or 221 failures occur. One of the requests thatcan be made of TST task is that of restarting the timeout activity on aloop under test so that any access may be held for longer than theinitial timeout value if required.

After initiating the timeout activity on loop access, TST task processesany request message in the table as follows. A `current count` variablethat has been preset by ACC task has a value equal to the number ofbytes taken by the access request data. In addition, each message bufferhas a field called `nbytes` that contains a count of the number of bytesof meaningful data contained in the buffer. If `current count` equals`nbytes`, the message contained only the ACCESS request, and TST taskarranges to send the response message associated with the initial ACCESSrequest in the UP direction. If, however, current count is less than`nbytes`, then test requests have been included with ACCESS request, andTST task proceeds to process those other requests. This processingactivity is described in the subsequent paragraphs. For each testrequest found in the request message, TST task arranges for the requestto be performed, collects the response in the associated responsemessage buffer, and when the last request has been processed, returnsthe response message to the FE computer 220 or 221 making the requests.If the last request processed was not one to drop the test access, TSTtask then waits for the arrival of a new message containing testrequests. In this way, the FE computer guiding the testing can requesttests to be performed, analyze results and determine the next test to beperformed according to its embedded adaptive test algorithms.

Whenever the associated FE computer 220 or 221 transmits a new messageof test requests DOWN the hierarchy for a loop already accessed via aparticular LTS port 2801-2816, that message is received by the SERIALDATA task and routed to the appropriate TST task. The HEADER portion`down-parameter` byte contains the port identifier, and a dynamic tablein LTS controller 2000 is used to determine the specific TST taskgoverning activity on a specific port.

The TST task is schedules to RUN when the new request message is sent toit. The TST task attaches the message to the temporary table referred toabove, and sets `current count` equal to the size of the message HEADER.Consequently, `current count` has the offset of the first byte after themessage HEADER, which is the first request in the present message. Thisis depicted in FIG. 16. A message buffer is now obtained from OS,attached to the table, and used to accumulate responses to the requestsspecified in the REQUEST message.

Before processing any test requests, TST task determines if a DDDcallback is associated with the loop under test. If so, the callbackpath is placed in the so-called HOLD mode so that testing can beperformed on the loop while the callback path is still held up. The talkcircuit `mode` (either HOLD, TALK or MONITOR) is saved for restorationupon completion of test request processing. In this way, tests areperformed on a loop with an associated callback, and the loop issubsequently restored to the callback state that existed prior toreceipt of the request message. The callback state can be changed by arequest in the message that simply causes LTS controller 2000 to changethe value of the remembered state. When the remembered state isrestored, a new state is actually effected for the callback path.

The TST task divides test requests into two categories, namely, thosethat can be performed by either LTS controller 2000 or port controller2200, and those that require the services of one PMU 2101-2103. If therequest is to be performed by a PMU 2101-2103, TST task attempts to haveallocated to it an idle PMU. If no PMU is available, a `status` of BUSYis set for the test request, no further processing of requests iscarried out for the current request message, and the accumulatedresponses are returned to the FE computer supervising the testing. If,however, a PMU is allocated to the TST task, a message buffer isobtained from OS, the PMU request is formatted in this buffer, and thebuffer is sent to PARALLEL DATA task for transfer to the PMU. A timeoutis started on the request. If the timeout expires before the PMU returnsthe test results, a timeout failure status is recorded in the resultsbuffer, further processing of requests in the present buffer isterminated, and the accumulated results are returned to the supervisingFE computer. If the PMU returns the test results within the time limit,the status and results data are stored in the associated results buffer,`current count` is incremented by the number of bytes required for thejust processed test, and TST task determines if the request messagecontains another test request. This determination is made by comparing`current count` with the `nbytes` field in the request message. Since`current count` is incremented with each request processed, iteventually equals or exceeds `nbytes`, and processing for the presentrequest message is terminated; the buffer of the accumulated responsesis returned to the proper FE computer.

If the request is determined to be one that LTS controller 2000 canrespond to directly, it does so, and accumulates the response in theassociated response buffer. `Current count` is incrementedappropriately. If the request requires the services of port controller2200, a new message buffer is obtained from OS, a request message isformatted for port controller 2200, and the message is sent to PARALLELDATA task for transfer to port controller 2200. A timeout is initializedby PARALLEL DATA task, and if it expires before the response from portcontroller 2200 is received, the timeout sequence is executed, asoutlined above for the timed-out PMU request. If the response isreceived within the time limit, the response buffer is updated with theresults, `current count` is incremented by the appropriate amount, andprocessing continues for the next test request, if any.

The above discussion shows that LTS controller 2000 is capable ofprocessing concatenated test requests received in a single requestmessage. The only restriction is that the responses to all requests mustfit into the response message buffer. As each message is processed, aPMU 2101-2103 is attached to TST task, if necessary. This PMU remainsassociated with TST task for the duration of processing of the presentrequest message, but is freed for use by another TST task for servicinganother loop accessed on another port when processing is completed forthe present request message.

As mentioned earlier, LTS 160 can be equipped with up to sixteen ports2801-2816 and therefore can support concurrent testing on sixteen loops.Sixteen instances of TST task allow this processing to occur, and OS isthe multitasking support for the simultaneous testing.

The timeout mechanisms described in the above paragraphs of this sectionserve to insure that resources of LTS 160 are not lost to the system incases where errors occur. For example, without a timeout facility, if aPMU should reset in the middle of a test request, the loop access, theassociated port equipment and any associated talk circuit would bepermanently stuck awaiting a response that could never occur. All thisequipment would be unavailable to the MLT system in the sense that itcould not be used again because of its permanent BUSY status. Thetimeout facility overcomes errors of this sort by causing error routinesto execute and free associated equipment. The overall timeout on theloop access, started by TST task as soon as loop access is completed,overcomes the error condition that prevails when TST task is awaitingthe next request message for the FE computer, but that computer fails.Since the knowledge of the FE computer regarding accesses prior tosystem failure is most likely lost, the next message may never arrive.LTS 160 resources are likewise lost in this case without the timeoutmechanism because this equipment cannot be used by other FE computers,or indeed, by one that failed and is now back on-line.

2.2.1c LTS Requests

With the presentation of the above structure and operation and theintroduction of certain nomenclature, it is now appropriate to present alist of requests, including other access or test types, processed by atypical LTS 160. The list shows the subsystems, that is, PMU 2101-2103,LTS controller 2000 or port controller 2200, that actually performs therequest, and indicates the level of activity, where appropriate,required to respond to the request.

1. DROP ACCESS--drop the loop test access and also any DDD callbackassociated with the loop. The port controller is required to performthis request. A signaling algorithm is executed to alert the test trunkcircuit that access is to be dropped. The LTS controller needs to freeall equipment associated with the access.

2. DROPDDD--drop the DDD callback connection and free the associatedtalk circuit. Relays are activated on the appropriate talk circuit, andthe switching machine appearance of the callback line is opened toindicate "off-hook". This request is performed by the LTS controller.

3. TALK--put the associated DDD callback path into the mode that allowsthe Maintenance Center administrator to talk to the customer or craft atthe end of the loop under test. The LTS controller causes relays to beoperated on the talk circuit.

4. HOLD--put the associated callback connection into the mode thatallows testing to be carried out, but which keeps the callback pathconnected. Talk circuit relays are operated by the LTS controller.

5. MONITOR--put the associated callback connection in the mode thatprovides a high impedance bridge connection, so that the MaintenanceCenter administrator can listen on the tested loop. Talk circuit relaysare operated by the LTS controller.

6. MON₋₋ TEST--keep the high impedance monitor mode on the callbackconnection while the next test is performed, so that the MaintenanceCenter administrator can listen on the tested loop while the test isbeing performed. Talk circuit relays are operated by the LTS controller.

7. RING--attach ringing distributor circuit 2500 to the loop under test,and apply ringing voltage according to the ON-OFF code contained in therequest message. Also, monitor for the ring-trip (customer off-hook)indication, and connect a gain amplifier to the callback path, ifrequired. Relays are operated by the LTS controller on both the talkcircuit and on the ringing distributor circuit.

8. GAIN--allocate an amplifier circuit to the loop under test, andconnect the amplifier to the associated callback connection. Talkcircuit relays are operated by the LTS controller.

9. NOGAIN--remove the gain amplifier associated with the callbackconnection. Talk circuit relays are operated by the LTS controller.

10. DELAY--wait for the specified time interval before executing thenext test request. The function is provided by the LTS controller, usingthe OS timeout facility.

11. KEEP₋₋ EQT₋₋ SETUP--terminate processing for the present requestmessage, but do not free the PMU now allocated for testing the givenloop. This feature is provided by the LTS controller.

12. SHRT₋₋ DETECT--monitor the loop for a short condition (less than 30Kohms) between either conductor and ground, or between the two loopconductors. This feature is provided by the port controller, andrequires that a DC source be applied to the loop, and that the loopcurrent be monitored for state changes.

13. ITA--manipulate sleeve lead current to activate the central officein-band signaling circuit, so that a test of the customer's key pad canbe performed by the port controller. A source is applied to the sleevelead.

14. TRACING₋₋ TONE--apply a continuous tone from tracing tone source2900 to the loop under test, so that craft personnel can locate the pairunder test in the outside plant. The continuous tracing tone sourcevoltage of the LTS is applied to the loop under test in either ametallic or longitudinal mode, as per the request parameter.

15. The following five requests deal with sleeve lead control circuit2500, and are used for signaling the central office equipment to attachcertain equipment or to perform some service. All sleeve leadmanipulation is done by the port controller by applying a DC source tothe sleeve lead circuit 2500.

a. HI₋₋ NEG₋₋ SLEEVE--high sleeve current with negative battery

b. LO₋₋ NEG₋₋ SLEEVE--low sleeve current with negative battery

c. OPEN₋₋ SLEEVE--open circuit the sleeve lead

d. HI₋₋ POS₋₋ SLEEVE--high sleeve current with positive battery

e. LO₋₋ POS₋₋ SLEEVE--low sleeve current with positive battery

16. HAZ₋₋ POT₋₋ STATUS--check for the existence of a hazardous potentialon the loop under test (port controller) by querying a thresholdingcircuit.

17. AUX₋₋ CONNECT--connect two loops to a single PMU to allowdouble-sided resistive fault sectionalization tests to be performed. TheLTS controller performs this operation by operating relays.

18. CALL--by manipulating relays and circuitry on the associated talkcircuit, place a low impedance across the line circuit of the loop undertest, so that a Maintenance Center administrator can simulate customerdialing action. This facility is provided by the LTS controller.

19. EXTEND₋₋ TO--change the overall timeout on the loop access to thevalue specified in the present message (LTS controller).

20. CON₋₋ TP₋₋ SLV--connect tip to sleeve in order to diagnose testtrunks. The port controller provides this feature by operating relays inthe port circuit.

21. DCON₋₋ TP₋₋ SLV--disconnect tip and sleeve (similar to the aboverequest).

The following requests are performed only by the Precision MeasurementUnit 2101, 2102 or 2103; the listing is exemplary of the type of testingeffected by a PMU.

1. AC3TY--apply AC sources and measure resultant current to producevalues that yield a Thevenin equivalent circuit for the loop at theapplied frequency.

2. ACDC₋₋ I--short circuit the loop conductors to ground, and measurethe resultant current flows.

3. BAL--apply a balanced AC source to the loop, and measure theresultant loop longitudinal balance.

4. DCT--produce only the DC portion of the DC3TY test summarized below.

5. DC3TY--apply both DC and AC sources to the loop, and measure theresultant currents used to calculate an AC and DC Thevenin equivalentcircuit for the loop.

6. DTA--draw dial tone from the central office, and measure thecharacteristics of the dial tone signal sent over the customer loop.

7. FREQ₋₋ DETECT--measure the signal level at the frequency specified inthe request data.

8. THEV--execute a special DC measurement sequence for generatingcurrent measurements in cases where a Thevenin equivalent circuit is tobe obtained for a circuit known to have low resistance values.

9. OCFEMF--measure open circuit foreign voltage present on the loopunder test.

10. PBX3TY--execute a special DC and AC test algorithm for generatingdata used to determine the Thevenin equivalent circuit for PBXequipment. The PBX attendant is not alerted by the application oftesting voltages.

11. PBXDCT--same as PBX3TY, but for a DC characterization only.

12. RCNT--determine the number of ringers present on the loop under testby making a series of AC current measurements when sources of variousfrequencies are applied to the loop.

13. RDA--alert the customer to start dialing a digit zero on the dial,and measure the dial parameters.

14. ROH₋₋ RLS₋₋ TNK--execute an algorithm that causes release of apermanent signal circuit so that the receiver-off-hook test can beperformed.

15. ROH₋₋ SPUR--measure the presence of spurious signal energy at thefrequencies used in the receiver-off-hook measurement.

16. ROH₋₋ TEST--apply the receiver-off-hook test signal, and measureloop currents at harmonic frequencies.

17. ROH₋₋ VFB--apply a source voltage and measure the resultant loopcurrent in order to approximate the length of a loop with a TIP-RINGshort.

18. SOAK--apply a sequence of DC sources to the loop, and measureresultant current flows.

19. THERM--apply a high level AC voltages to the loop, and measure theresultant current flows to detect a thermistor.

20. SSRFAULT--execute the single-sided resistive fault sectionalizationmeasurement algorithm.

21. CN₋₋ DTF--totalizer detection for a coin-first coin telephone set.

22. CN₋₋ TOT_(--DTF--totalizer) homing function for a coin-first cointelephone set.

23. CN₋₋ CF--determine the resistance of the coin circuit totalizer sothat proper current can be applied to home it.

24. CN₋₋ TOT₋₋ CF--home the coin circuit totalizer, and monitor forcurrent flow.

25. CN₋₋ RDET--measure the resistance of the coin relay in order todetermine the proper source for the coin return function.

26. CN₋₋ RCR--apply sources to proper polarity in order to collect orreturn a coin in a coin telephone set.

27. CN₋₋ GRFV--measure the resistance of the groun path in a coin set.

2.2.1d LTS Controller Circuitry

Each controller within LTS 160, namely, LTS controller 2000, portcontroller 2200 and a controller embedded within each PMU 2101-2103 (tobe discussed in a later section), is implemented with basically the samecircuit topology; it comprises a microprocessor device and ancillarysupport device. This topological arrangement is now presented withreference to LTS controller 2000. Because of its similarity to the othertwo controller types, the description applies to the latter twocontrollers with variations easily recognized by those skilled in theart.

LTS controller 2000 is composed of a microcomputer-based CPU, read-onlymemory (ROM), random access memory (RAM) and input/output facilities(I/O). Also provided is an interrupt structure allowing asynchronousevents to be recognized and acted upon in an order-of-priority manner aswell as suitable system timing.

The CPU is implemented with an 8-bit microprocessor having a 16-bitaddress bit, thereby allowing access to 64K bytes of memory. Themicroprocessor has a memory-mapped I/O structure that allows forallocating a portion of the memory address space for I/O deviceselection. For LTS controller 2000, 8K of the upper address space isallocated to I/O (as contrasted to 6K for port controller 2200 and 4Kfor the PMU controller).

Of the remaining memory associated with LTS controller 2000, 16K isprovided by RAM and 40K by ROM. Of the latter memory, 20K is common toall software operations, and 20K is bank switched so that one of threedifferent segments may be operational during a given processingsequence. (For port controller 2200, the memories implemented comprise18K of RAM and 40K of ROM, the latter having two 24K switched segments.For the PMU controller, 16K of RAM is augmented with 48K of ROM, 16K ofwhich is switched from one of four banks). Actually, address decoding inthe 64K byte addressing space is ROM programmable, thus allowing memoryallocation and I/O functions to be placed in any segments desired, sothe above allocations describe but one illustrative embodiment.

One I/O function requires communication via the GPIB protocol, and thisis typically implemented with a standard GPIB adapter device. Anotherrequired I/O function is communication in a serial, bit-oriented moderequired by the high level data link protocol. Again, an appropriatecommercially-available device interfaces to the memory-mapped space.Finally, an interface is provided for standard direct memory access(DMA) devices to provide handshake conditioning for the high-speed datachannels if an increased throughput rate is required.

Two programmable devices complete the basic implementation of LTScontroller 2000; these include a programmable interrupt controller (PIC)and a programmable interval timer (PIT).

The PIC device typically supports eight vectored interrupts with eithera fixed or rotating priority. Each input can be individually masked viasoftware control. Two of the interrupts are used in conjunction withGPIB and PIT devices. The latter input provides a crystal controlled,timed-interval interrupt that allows real-time clock applications suchas system time-out functions.

The PIT contains three independent 16 bit counters. Each counter hasoperational modes to provide various counter/timer functions such asevent counting, square-wave generation and software controlled stroking.The clock input to the clock divider circuit is provided by a 4 MHzcrystal. The output clocks range from 15.625 kHz to 2 MHz and one may beselected to drive the CPU microprocessor.

2.2.2 Port Controller

Port controller 2200 is also a microcomputer-based system running underthe same operating system (OS) as DCN 140 and LTS controller 2000. Inport controller 2200, the following tasks may be identified:

(a) PARALLEL DATA task controls the transmission and reception ofmessages over bus 20001, which typically implements the GPIB protocol.It communicates with the corresponding task in LTS controller 2000 andis similar in structure and operation, the main difference being thatthe PARALLEL DATA task in LTS controller 2000 serves as the bus master.

(b) ACCESS/TEST task executes the access algorithm for NTT and MDFaccess. This includes control of the following devices: (1) portcircuits 2801-2816 and corresponding sleeve circuits 2817-2832 toconnect to the appropriate no-test trunks 9401-9416 and to control themagnitude and polarity of sleeve current; (2) trunk dialer 2650, ofeither the dial pulsing or multifrequency type, depending on the centraloffice switch type; (3) busy/speech detector 2600 to determine DC busyand speech busy conditions; (4) tracing tone source 2900 for long termapplication of pair identification tones for the loop; and (5) P CONTROLsection 2702 of EAN 2700 to guide access and then connect theabove-identified devices to the accessed pairs when required. There area maximum of sixteen active ACCESS/TEST tasks, one for each port/sleevecircuit. However, the task-to-port assignment is not fixed, but ratherdynamically allocated depending on the number of active accesses.

(c) ADMINISTRATION task performs all administrative functions in portcontroller 2200, including energizing the internal timer periodically soas to preclude a system reset as well as accepting data base downloadsat system initialization. Again, the task structure is similar to theADMINISTRATION task of LTS controller 2000. The system reset istransmitted DOWN bus 20001 from LTS controller 2000 to all LTS 160components once a reset request is initiated UP the hierarchy.

(d) DUMP MEM task is activated after a microprocessor malfunction and isarranged to provide for transmission of blocks of memory to LTScontroller 2000; the memory snapshot focuses on the task that was activewhen the malfunction occurred.

(e) DIAGNOSTICS task provides self-test capabilities for the hardwarecontrolled by port controller 2200 as well as interfacing to self-testsfor LTS controller 2000 and PMU's 2101-2103.

Further discussion with respect to port controller 2200, particularlytask processing, is deferred to Section 2.2.4 so that the descriptionrelating to PMU's 2101-2103 may be integrated into the operationaldescription.

2.2.3 Precision Measurement Unit (PMU)

FIG. 17 depicts, in block diagram form, the structure of PMU 2101 (PMU2102 and PMU 2103 of FIG. 11 are essentially the same as PMU 2101 so itis taken as representative). PMU 2101 is a microprocessor controlled,general purpose test instrument in that no part of PMU 2101 is dedicatedto performing any particular test and this unit serves as the primarymeans for measuring the electrical parameters of the subscriber loopunder test. The following interrelated subsystems comprise PMU 2101: PMUcontroller 3100; source generator 3200; source applique 3300; detector3400; measurement processor 3500; and digital signal processor 3600.Subsystems 3200 and 3300 are connected in cascade and this cascadearrangement serves to generate and couple the requisite signals neededfor testing to subscriber loops (180 or 181 of FIG. 2). Detector 3400,in conjunction with applique 3300, serves to detect currents on the loopunder test and to convert these currents to corresponding voltages.Subsystems 3500 and 3600 comprise a series combination which processesthese voltages and formats the processed signals for transmission,ultimately, to FE computer 220 or 221 (FIG. 2). In the local PMUenvironment, PMU controller 3100 receives test requests from LTScontroller 2000 (FIG. 11) over parallel-oriented bus 20001, sets up thetest by interfacing to the various subsystems via its buses 31001 and31002, and transmits the results of testing across bus 20001 uponcompletion of testing.

Source generation subsystem 3200, depicted in block diagram form in FIG.18, produces (i) the requisite AC and DC signals that are applied toloop 180 or 181 via TIP lead 32002 and RING lead 32003, and (ii)demodulating signals, on leads 32004 through 32007, necessary to drivemeasurement processor 3500. Generator 3200 is adapted to providecomposite AC-DC signals simultaneously to TIP lead 32002 and RING lead32003. To insure resolution of fault conditions within predeterminedtolerances, generator 3200 is arranged to produce:

(a) a single AC signal having a frequency from 1 Hz to 3200 Hz in 1 Hzsteps at voltage levels from 0.0 v to 12.75 v rms in 0.05 v steps andfrom 12.8 v to 95.6 v rms in 0.4 v steps. The accuracy is ±0.1 v rms or3%, whichever is greater;

(b) a DC signal at a level from 0 to ±51 v in 0.2 v steps and from±51.15 v to ±135.3 v in 0.55 v steps. The accuracy is ±0.1 v or 2%,whichever is greater;

(c) a swept frequency signal where the starting frequency, stoppingfrequency and frequency increment may be specified within broad limits;

(d) a pulsed tone whose rate and duty cycle may be specified over abroad range;

(e) a signal comprising the sum of two AC signals having the samerelative amplitude; and

(f) a signal formed by sequencing through 10 tone pairs each of whosefrequencies may be specified over the range from 1 Hz to 3200 Hz andwhose durations and silient intervals may be specified.

Besides producing the aforementioned signals (a)-(f), generator 3200 mayalso be configured so that different DC levels may be applied to TIP andRING leads 32002 and 32003, respectively, at the same time or that theapplied AC signals have the same amplitude but are phase-shifted 180degrees relative to each other. Moreover, combinations of an AC signaland a DC signal, as defined in items (a) and (b) above, may be providedas long as the peak value of the composite signal is less than 135.3volts.

Source generator 3200 typically comprises a set of microcomputers (notshown in FIG. 17). Each of these microcomputers generates digitalsamples via a table lookup technique. For AC signals, these digitalsamples are converted to analog form by means of digital-to-analog (D/A)converters embedded within generator 3200. Composite signals are formedby combining the outputs of the D/A converters with a DC level.

The MLT performs mainly admittance measurements. In order to testsubscriber loop 180 or 181 of FIG. 2, the signal voltages present onoutput leads 32002 and 32003 emanating from generator 3200 are applied,via source applique 3300, to TIP and RING leads 33001 and 33002,respectively. The resultant longitudinal-mode current flowing in leads33001 and 33002 are each independently detected in applique 3300 bymeans of a magnetic sensing circuits (not shown). The outputs of themagnetic circuits are signals proportional to the detected currents andthese signals appear on multiple leads 33003 and 33004 emanating fromapplique 3300. Detector 3400 receives and then converts these signals tovoltages proportional to the sensed currents. Output leads 34001 and34003 from detector 3400 carry voltages proportional to TIP current inthe usual measurement mode, whereas output leads 34002 and 34004 havevoltages proportional to RING current. There is also a measurement modewherein applique 3300 and detector 3400 can be configured to producevoltages proportional to a longitudinal current and the metallic currentassociated with the loop under test.

The signal processing section of PMU 2101 comprises: measurementprocessor 3500, with circuitry including multipliers, analogmultiplexers, analog-to-digital (A/D) converters and sample-and-hold(S/H) circuits; and digital signal processor 3600. In-phase (TIP(I) andRING(I)) and quadrature (TIP(Q) and RING(Q)) waveforms at precisely thefrequency applied to the loop under test represent one arrangement ofsignals present on leads 32007, 32005, 32006 and 32004, respectively.These waveforms may be produced in generator 3200 as the counterparts tothe signals applied to the loop under test and these four waveforms areused to synchronously demodulate the voltages produced by detector 3400on leads 34001 and 34002. Analog multipliers embedded within processor3500 perform the demodulation. For instance, the output of onemultiplier is a signal formed by multiplying the first detector voltage,on lead 34001, by the in-phase component of the signal on the TIP(TIP(I)) appearing on lead 32007. If the voltage on lead 34001 is theresult of current flow on the TIP of the loop under test, then thesignal from this multiplier is proportional to the real part of theadmittance-to-ground of the TIP conductor.

Anticipated phase shifts both within circuitry of PMU 2101 or due toexternal circuitry can be accounted for and accommodated simply by phaseshifting the demodulator signals appearing on leads 32004 through 32007relative to the sources applied to the loop via leads 33001 and 33002.In addition, harmonics of the frequencies applied to the loop under testcan be generated within source 3200 and used to detect nonlinearities inthe loop admittance by searching for DC components in the outputs of themultipliers. The use of two signal conditioning channels (34001 and34002) and four demodulating signals (on leads 32004 through 32007)allows PMU 2101 to make multiple measurements simultaneously. In theembodiment, the results of all measurements are DC values, eitherinitially or after the demodulation process.

Measurement processor 3500 is used to select from among the variousoutputs appearing simultaneously from the multiplier outputs anddetector leads 34001 through 34004. The signals so selected, typicallyin pairs, are fed to S/H and A/D circuits contained within processor3500. The digital samples, emanating from processor 3500 on oneconductor of multiconductor 35001, serve as input to digital signalprocessor (DSP) 3600. DSP 3600 implements several digital filteringprograms, one of which includes a dynamic settling algorithm that isutilized to decide when a final value has been obtained from ameasurement. Test results are passed from DSP 3600 to PMU controller3100 over bus 31002.

As indicated by the foregoing discussion, PMU 2101 effects, withinpredetermined voltage and frequency limits, measurements to characterizea three terminal network, including those of a distributed parameternature exemplified by a two-wire, shielded transmission line (that is,the customer loop).

2.2.3a Digital Signal Generator (DSG)

The procedure used to generate cosinusoidal waveforms with generator3200 of FIG. 17 involves accessing signal values that have been storedwithin its read-only memory. The values that are selected according tothe technique to be described are transformed into a cosinusoidalwaveform via a digital-to-analog converter and low-pass filter means.

The values stored within the memory of generator 3200 are, basically,magnitude samples of cos θ for the first and third quadrants. Althoughsymmetry of a cosine wave would permit its reproduction from samples ofone quadrant only, higher frequency signals are effected by providingtwo sets of samples to reduce transformation time in matching thesamples to a form acceptable to the digital-to-analog converter.

The values for each quadrant are accessed with an eight-bit address, so256 memory locations per quadrant are stored. The memory for the firstquadrant stores +cos θ over the range 0 to 90 degrees with θ having aspacing of 0.3516 degrees (90 degrees/256), whereas the other memorystores -cos θ with the same spacing.

Each of the values stored in the memory is contained within an eight-bitword. Each value is an integer representation of the decimal numberobtained by evaluating the cosine with the foregoing spacing. Thus, ifc(n) represents the nth value, the integer stored at the nth address is##EQU1## where I[.] designates an integer truncation operation to 8 bitsand n is such that 0≦n≦255. The multiplicative factor 256 in equation(1) basically left-shifts the decimal values resulting from truncation.(If the memory word-size is, in general, K, and the number ofaddressable locations in memory is 2^(L), then equation (1) has the form##EQU2## for 0≦n2^(L) -1, which reduces to equation (1) for K=L=8).

The -cos θ table, that is, the values in memory associated with thirdquadrant samples, is the 2's complement version of the +cos θ table. Thecomplementary relationship of these two tables saves execution time thatwould be needed to generate the complementary values if only firstquadrant values were stored. Since the particular embodiment of thepresent invention utilizes a digital-to-analog converter requiring anoffset binary code to produce a four quadrant waveform, any table valuerequires only the insertion of the proper quadrant sign value tocomplete the offset binary code.

Besides the +cos θ table, generator 3200 utilizes an accumulator toobtain a sample index and quadrant pointer. With reference to FIG. 19,the accumulator comprises registers 3210, 3211 and 3212 which,typically, represent three contiguous bytes (8-bit words) in memory. Theboundaries for these three bytes are chosen such that bits 0 and 1 ofthe high byte (register 3210) contain quadrant information in the formof a quadrant pointer. For instance, if these two positions had thebinary values `0` and `1`, respectively, then third quadrant values arerequired. The quadrant information is passed to sample selector 3213 onlead 3251. The entire middle byte, comprising register 3211, providesthe address of the sample to be selected by selector 3213. This address,called the sample index, is passed to selector 3213 viaparallel-oriented bus 3252. Bits 4 through 7 of the low byte (register3212) contain the four least significant accumulator bits.

Frequency generation is accomplished by the binary addition of a 12-bitfrequency word, arriving on bus 3254, to the 12 least significant bitsof what is, in effect, a 14-bit accumulator. The frequency word on bus3254 is indicative of the frequency of the cosine to be generated, asexplained shortly. The addition occurs at a fixed rate, designated f_(s)(Hz), which is typically at least twice the highest frequency cosinusoidto be provided by generator 3200.

In general, as the frequency word is added to the accumulator at therate f_(s), the bits of register 3212 eventually overflow into register3211. In turn, register 3211 eventually overflows into register 3210.After each addition, the two bits of register 3210 are checked for phaseinformation and all bits of register 3211 are passed to selector 3213. Acosine magnitude value is appropriately extracted from the +cos θ tablesstored within selector 3213. A polarity sign is supplied to the value,and the now completed encoded value is passed to digital-to-analogconverter 3214 via bus 3253.

In view of the foregoing discussion, if a cosinusoidal frequency of 1 Hz(having a frequency word representation of 00000000 0001 in binary) isto be generated, then it would require sixteen additions to theaccumulator (initialized to 00 00000000 0000) before register 3212overflows into register 3211. This means that for one complete cycle,wherein the tables will be indexed exactly 1024 times, one table valueis accessed sixteen consecutive times, another value sixteen consecutivetimes, and so forth. Thus the same encoded cosine value is loaded intoconverter 3214 sixteen times before a new encoded value becomesavailable. However, if a frequency word of 00000001 0000, representing16 Hz, is added to the accumulator, then 1024 sample indices are stillproduced, but a new and different encoded cosine value is loaded intoconverter 3214 after every addition. To reiterate, if the frequencyrepresented by the frequency word is small (<16 Hz), the cosinemagnitude values do not change rapidly, that is, they become "dwelled"on for a period of time, whereas for a longer frequency word (≧16 Hz),the cosine samples change rapidly.

The result of this generation technique is a cosinusoidal wavesynthesized by stepping through a look-up table, small steps for lowfrequencies and large steps for high frequencies. The frequency spectrumfor a wave synthesized in this manner contains the desired fundamentalfrequency plus its harmonics. Also present is the sampling frequencyf_(s) and its harmonics. Moreover, the desired frequency and itsharmonics are centered about f_(s) and its harmonics. To reducedistortion due to aliasing, f_(s) is at least twice as great as thehighest frequency to be produced. In addition, a low-pass filter,designated as filter 3215 in FIG. 19, removes frequency components abovef_(s) /2, thereby providing a smoothing operation.

Besides the frequency components discussed above, there are undesiredfrequencies due to dwelling on table values during the generation of lowfrequencies and the finite precision of converter 3214. Thesefrequencies are subharmonics and filter 3215 cannot remove them sincethey fall within the passband. Fortuitously, however, the amplitudes ofthe subharmonic components are small due to minor differences inadjacent table values and for converter precision on the order of eightbits per sample; therefore, the harmonics are tolerable without furtherprocessing.

2.2.3b Magnetic Current Sensor

As briefly discussed above with reference to FIG. 17, source applique3300 and detector 3400 combine to detect appropriate conductor currents,typically longitudinal mode currents in both the TIP and RING of theloop under test, and then to convert the detected conductor currents tovoltages, suitable for processing.

A more detailed block diagram of source applique 3300 is shown in FIG.20. Signals transmitted from source generator 3200, via leads 32002 and32003, serve as inputs to TIP source driver 3301 and RING source driver3302, respectively. Drivers 3301 and 3302 provide high impedancebuffering to the input signals and suitably level shifted output voltageor current signals to energize output TIP lead 33001 and RING lead33002, respectively. Source impedance values presented to the TIP andRING are effected by impedance network 3309 coupling drivers 3301 and3302 to leads 33001 and 33002, respectively. Drivers 3301 and 3302 andnetwork 3309 provide a high degree of testing flexibility. Voltages from0 to ±135.3 V peak and currents up to 125 ma can be delivered through avariety of source impedances. The choice of impedances ranges from ashort circuit up to 100K ohms in series with both TIP and RING or eachseparately. Moreover, TIP and RING can be shorted or capacitivelycoupled. Applique controller 3311 signals network 3309, via lead 33111,as to the desired coupling impedances. Controller 3311 operates inresponse to signals transmitted over busses 31001 and 36001.

Magnetic core pair 3305,3306 associated with TIP lead 33001 and corepair 3307,3308 accompanying RING lead 33002 detect flux changes inducedby current carrying conductors which are wound through the coreapertures. For instance, with the relay contacts of relay A in the makeand break positions shown in FIG. 20, the TIP lead current on conductor33001 forms a two-turn winding on each core 3305 and 3306; similarly,the RING lead current on conductor 33002 penetrates the apertures ofcore pair 3307,3308 twice with the same orientation. However, if relay A(which is embedded within applique controller 3311) is energized, thencore pair 3305,3306 encompasses the TIP lead only once and the currentin the RING lead is also routed through core pair 3305,3306, but in asense opposing tip lead current. In effect, core pair 3305,3306 detectsa differential between the individual currents flowing in the TIP andRING leads 33001 and 33002, respectively. Thus, the two operating modesof relay A determine the desired routing of current carrying pathsthrough core apertures. More complex relay arrangements enable numerousmeasurement modes as well as fault location procedures for a variety ofloop fault conditions. Loop fault detection and location methodologywhich utilizes the foregoing current routing arrangement is the subjectmatter of U.S. patent application Ser. No. 308,417, filed on Oct. 5,1981, by J. M. Brown and assigned to the same assignee as the instantapplication. A synopsis of this loop fault locating methodology will bepresented in Section 3.2.1d wherein the MLT system tests are defined.

Core pairs 3305,3306 and 3307,3308 are typically matched ferrite cores;matching is required to minimize offset drift as ambient conditions,particularly temperature, vary. With the core pairs and accompanyingcircuitry of the illustrative embodiment, currents from 1 ua to 500 main the DC to 3200 Hz frequency band may be measured with an accuracy of±1 ua or ±1% for the anticipated ambient conditions.

A brief description of the operation of one core pair arrangement ispresented with reference to FIG. 21. Each core 3307 or 3308 hasbasically three windings. One winding, designated the line, winding,comprises conductor 330013 in series with conductor 330014; theseconductors are considered to form one winding because each provides aseries aiding field excitation. The conductor having ends 330041 and330043 forms a sense winding, whereas the conductor having ends 330042and 330044 comprises a control winding on each core 3307 and 3308. Withthe currents I_(L), I_(C) and I_(S) flowing in the line, control andsense windings, respectively, and having the flow direction shown inFIG. 21, the line winding and control winding on core 3307 provideseries-aiding magnetizing fields whereas the fields are series-opposingon core 3308, and each sense winding provides series-opposing fields tothe line winding fields.

Operational amplifier 34021 and capacitor 34024 form an integrator whichacts to feed back current I_(S) through the sense winding on each coreto cancel magnetic flux caused by the current I_(L) in the line winding.In steady-state operation, that is, after line current transients havedissipated, the voltage on output lead 34012 is proportional to thecurrent I_(L) on lead 330013 (or 330014). In order to determine if I_(S)is of sufficient strength to cancel I_(L), pulse generator 34022periodically drives cores 3307 and 3308 into saturation through theseparate control winding of each core. During the interval that cores3307 and 3308 are driven into saturation with current I_(C), switch34028 remains open. When the saturation pulse is removed, switch 34028is connected to the inverting (-) input of amplifier 34021, throughresistor 34027, in order to sense the presence of an error voltagegenerated by collapsing flux, that is, flyback from saturation. If thenet flux caused by fields induced by I_(S) and I_(L) current is zero,the voltage generated on each sense winding is equal and opposite and,consequently, the error voltage is zero. However, if the net flux is notzero, the nonzero error voltage is integrated and stored by capacitor34024. During the next pulse cycle, the stored voltage furnishes currentI_(S), through resistor 34023, to the sense windings and, accordingly,forces the net flux to zero.

If cores 3307 and 3308 are not perfectly matched, primarily becausetheir characteristics do not track during changing ambient conditions, anonzero error voltage may be generated even if the line winding currentis zero. To partially correct for core offset, a compensating offsetcurrent is fed into integrator amplifier by offset voltage corrector34025 in series with resistor 34026. After offset correction, the outputvoltage on lead 34012 substantially tracks the line current. In theillustrative embodiment, automatic offset correction achieves a twoorders of magnitude improvement in detection performance as compared tothe circuitry without offset compensation; automatic correction occursperiodically, although for the most sensitive measurements, a correctionis made immediately prior to a measurement. Offset corrector 34025,which is typically a digital-to-analog converter, receives a correctionvoltage from PMU controller 3100 on bus 35052. The voltage supplied byPMU controller 3100 results from a test measurement, with zero loopcurrent, performed on the periodic basis.

FIG. 21 depicts the essential circuitry of ring I-to-V converter 3402 ofFIG. 22. As shown in FIG. 22, ring I-to-V converter 3402 has acorresponding counterpart in tip I-to-V converter 3401 which performsbasically the same operation on core pair 3305,3306 of FIG. 20. Theoutput voltages proportional to TIP and RING lead currents appear onleads 34011 and 34021, respectively, of FIG. 22. In that each voltagesignal is processed in basically the same manner with the remainder ofthe circuitry embedded in detector 3400, only processing of the outputvoltage signal appearing on lead 34011 of tip converter 3401 isdescribed in the following.

The voltage on lead 34011 is band-limited to 3200 Hz by filter 3403. Forsome measurements, particularly in a high 60 Hz noise environment,filter 3403 also can provide 60 Hz band elimination filtering. Filter3403 operates under control of detector controller 3405, via lead 34053;in turn, detector controller 3405 receives instructions from PMUcontroller 3100 on bus 31001 and DSP 3600 on bus 36001. The filteredvoltage signal appears on lead 34031 and serves as an input to gainunits 3408 and 3410. Gain unit 3408 provides either a gain of four or nogain as well as filtering with a 10 Hz high-pass filter; the signal atthe output of gain unit 3408, on lead 34001, basically comprises only ACcomponents. On the other hand, the output of gain unit 3410, on lead34003, represents a composite AC-DC signal amplified by either a factorof four or directly coupled without gain. To determine which gain factorto apply, the outputs of gain units 3408 and 3410 serve as inputs tosaturation detector 3406. Initially, both gain units 3408 and 3410 areset to the maximum gain of four. If the signal at one or both outputs isabove a preselected threshold, saturation detector 3406 interrupts PMUcontroller 3100. Interrupt as a result of AC overload appears on lead34061, whereas composite signal overload is transmitted over lead 34062.Appropriate gain adjust signals are returned to gain units 3408 and 3410from PMU controller 3100 via detector controller 3405 and, particularly,leads 34058 and 34057. If saturation is still detected, then an inputattenuator is switched into the current path associated with TIP lead33001. The attenuator, depicted by element 3303 in FIG. 20, provides a4:1 current reduction. The signals thus appearing on AC-only lead 34001and broadband lead 34003 at the output of detector 3400 representsuitably scaled analog signals proportional to the currents flowing onthe loop conductor arrangement under test.

Now with reference to FIG. 23, additional processing is effected by themeasurement processor 3500 to prepare the analog signals for digitalfiltering in processor 3600 (FIG. 17).

The signal on AC-only lead 34001 is presented to 7-1 MUX, that is, theupper half of multiplexer 3501, on five parallel paths. The first pathdirectly couples lead 34001 to multiplexer 3501 so that broadband ACsignals may be measured. To obtain the signal on the second path,in-phase synchronous detection is effected by multiplying the voltagesignal on lead 34001 with the TIP (I) signal on lead 32007 infour-quadrant multipler 3701. Synchronous detection of the AC-onlysignal frequency shifts the information bearing components to DC forefficient filtering. Aliasing is mitigated with 10 Hz antialiasingfilter 3510 interposed between multiplier 3701 and multiplexer 3501. Thefourth path signal is obtained in a manner substantially equivalent tothe second path processing technique, the only difference being that aquadrature signal (TIP(Q)) serves as an input to multiplier 3702, vialead 32006. The DC components emanating from the second and fourthprocessing paths represent typically the real and imaginary parts of theadmittance with respect to ground of the loop conductor arrangementunder test, typically the TIP-to-ground path.

Oftentimes it is necessary to measure a current signal produced by avoltage arising outside the MLT system for which the exact frequency isnot known; in this case, synchronous demodulation is effected with anaverage frequency. For instance, dial tone provided to a telephone setis known to be in the 300 to 1000 Hz band. Synchronous in-phase andquadrature detection with a 650 Hz frequency, followed by filtering with350 Hz low-pass filters 3511 and 3513, respectively, results in signalsindicative of the presence of dial tone. The quadraturely-relatedsignals are delivered to multiplexer 3501 via multiplier filter pairs3701,3511 and 3702,3513, respectively, on paths three and five.

Finally, path six directly presents the broadband, composite AC-DCsignal to multiplexer 3501 and the signal on path seven results from lowpass filtering the signal on lead 34003 with 10 Hz filter 3514. Thislatter path is used primarily to measure the DC in the composite AC-DCsignal.

The seven TIP paths just described and duplicated by similar processingon the RING lead side and are received in the lower-half of multiplexer3501. The signals on all fourteen paths are present simultaneously.Analog multiplexer 3501 is used to connect one of the seven TIP pathsand a corresponding one of the RING paths to sample-and-hold (S/H)devices 3504 and 3505, respectively. Since programmable gain amplifier(PGA) 3502 is capable of processing only one input at a time,multiplexer 3506 performs time division multiplexing on the outputs ofS/H devices 3504 and 3505 and channels the desired signal to gainamplifier 3502 during appropriate time intervals. Lead 35011 couples theupper-half 7-1 MUX of multiplexer 3501 to S/H 3504, and lead 35041couples S/H 3504 to 2-1 MUX 3506. Similar functions are performed byleads 35012 and 35051, respectively. Finally, multiplexer 3506 and gainamplifier 3502 are coupled with lead 35061.

The output of gain amplifier 3502 serves as an input to twelve-bit A/Dunit 3503; coupling is via lead 35021. Gain amplifier 3502 provides gainfrom 1 to 256 in steps of 2. To determine the correct gain setting foreach sample presented to A/D unit 3503, two measurements are made persample. For the first measurement, PGA 3502 is set at unity gain. Thenumber of leading zeros in the 12-bit digital output on lead 35031 arecounted. For each leading zero, the gain is increased by a factor of twoup to a maximum gain of 256 or eight leading zeros. The signal is againmeasured and converted to a 12-bit digital signal. This two-stepmeasurement procedure ensures that the full conversion range ofconverter 3503 is utilized for maximum measurement accuracy. The 12-bitmeasured signal is combined with the setting on PGA 3502 to produce asignal requiring a maximum of 20 bits for complete representation.Digital signal processor 3600 is arranged to operate on these 20-bitsignals, as will be discussed shortly.

Because of the parallel processing arrangement of multipliers 3701through 3704 and time division multiplexing available with multiplexer3501, a number of analog signals resulting from a typical loopmeasurement can be processed essentially simultaneously. For instance,one measurement in the standard set of requests is the DC three terminaladmittance (DC3TY). With this measurement, both AC and DC sources areapplied between each loop conductor and ground, and the resultantcurrents are used to calculate an AC and DC Thevenin equivalent circuitof the loop. For instance, it is supposed that the AC voltage is appliedat 24 Hz. At a sampling rate of 100 Hz, the real and imaginarycomponents of the 24 Hz signal are processed on paths two and four andthe DC current on path seven for both the TIP and RING conductors,resulting in a total of six measurements from basically one sourcesignal.

Measurement controller 3507 provides the required timing information tosynchronize operation of multiplexer 3501, S/H devices 3404 and 3405 andmultiplexer 3506 to insure that the selected analog signals areavailable for A/D conversion in element 3503. In addition, controller3507 generates a progression of timing signals that activate, forexample: the first measurement with A/D converter 3503; the circuitry tocount leading zeros in data from the first measurement; the gainselection in PGA 3502 as determined by these zeros; the second A/Dmeasurement; and the transmission of the 12 bits representing a sampleto measurement interface 3508. Controller 3507 is dependent, initially,on information transmitted over bus 31001 from PMU controller 31001.Once activated, however, controller 3507 produces timing informationbasically independent of PMU controller 3100, although interrupts andreset requests may override and disable state timing.

Measurement interface 3508 serves a two-fold purpose, namely, (i) totemporarily store the results of the first and then the second A/Dmeasurements and (ii) to format the 12-bit data obtained from the secondmeasurement for transmission to DSP 3600. DSP 3600 manipulates 20-bit,two's complement data with the presumption that the least significantbit arrives first on its serial-oriented input port. In the presentsituation, this input port is connected to one conductor from channel35001 emanating from measurement interface 3508. Formatting is requiredsince data is transmitted serially between interface 3508 and A/Dconverter 3503 on one conductor of lead 35031 with the most significantbit arriving first. In formatting the data generated by the secondmeasurement, account is taken of the gain of PGA 3502, the polarity ofthe sampled signal and whether an extra gain, called "pseudo-gain", isto be implemented. The purpose of this extra gain is to reduce inherenterror in processing for low level signals due to a digital processingphenomenon called a "limit cycle" caused by finite word length effects.

FIG. 24 depicts how FIGS. 18, 20, 22 and 23 may be grouped to form acomposite of FIG. 17.

2.2.3c Signal Processing

The final stage in the processing of the detected TIP and RING signalsis effected by DSP 3600 of FIG. 17. DSP 3600 is controlled by PMUcontroller 3100 via bus 31002. PMU controller 3100 downloads therequired processing algorithm into DSP 3600 via memory bus 31002 andreceives results back over this same bus. This downloading featureallows DSP 3600 to perform a wide variety of filter functions eventhrough DSP 3600 has limited memory size. Nine different filteringfunctions are presently implemented in PMU 2101; these include:

(1) A DC-to-5 Hz low-pass filter function with 20 Hz attenuations of 40,80 and 120 dB. The amount of attenuation is selected on the basis ofinterference encountered in a particular measurement. The attenuation isselected in real time by a dynamic settling algorithm which releases themeasured data as soon as it has settled within prescribed limits,typically five consecutive measurements within one percent of eachother.

(2) A DC-to-5 Hz low-pass filter without settling with 120 dBattenuation at 20 Hz. The value of the output is provided upon demand byPMU controller 3100 as often as desired.

(3) A DC-to-5 Hz low-pass filter in which an in-phase/quadrature pair isconverted to a magnitude-squared value by a square and add operation.Results are provided as demanded by PMU controller 3100.

(4) A DC-to-5 Hz low-pass filter used for detection of asynchronoustones such as dial tone and in-band signaling. This filter programprovides the current filter output as often as it is requested by PMUcontroller 3100.

(5) A 5 Hz low-pass filter with peak detection. The peak value of thesignal is provided once on demand by PMU controller 3100.

(6) A broadband filter with mean-squared output using either 10 Hz to3200 Hz flat weighting or C-message weighting. Filter output is providedby DSP 3600 on demand.

(7) A program which counts the number of samples for which the inputsignal is above the given threshold and the number of samples for whichit is below the same threshold. Counting begins on the first high-to-lowtransition of the input or on the first low-to-high transition dependingon a parameter transmitted by PMU controller 3100. A count is returnedon each transition so that rotary dial pulses may be analyzed.

(8) A program which detects the voice-frequency range tone bursts fromcoin phone totalizers as well as the DC current flowing in the loopassociated with the coin phone. An indication is sent to PMU controller3100 after each tone burst is received. The value of the DC current isreturned after the last burst is received. Test timing is also includedin this program to identify continuous tones, no tones and test timeout.

(9) A program which performs self-diagnostic testing on DSP 3600,including its internal memory.

FIG. 18 indicates that DSP 3600 comprises basically two circuitelements, namely, digital filter 3601 and memory 3602. Digital filter3601 is implemented in the illustrative embodiment by a programmablesignal processor especially developed for digital filter-typeapplications requiring rapid multiplications and additions and thecapability of mitigating the effects of finite word length arithmetic.This programmable processor, however, has only 1024 addressablelocations in memory, which is the memory depicted by element 3602.Digital filter 3601 views this space as ROM and obtains its instructionsand data from this ROM space. On the other hand, PMU controller 3100views memory 3602 as RAM. This allows PMU controller 3100 to storenumerous programs in its own ROM (depicted as memory 3150 in FIG. 18),and by selecting one of the stored programs and loading it into DSPmemory 3602, PMU controller 3100 can effectively perform any necessaryfiltering or processing functions. Programs are downloaded from PMUcontroller 3100 utilizing the address and data portions of bus 31002 andthe results of processing operations in filter 3601 are passed back onthe data portion of bus 31002. Internal communication between filter3601 and memory 3602 occurs over bus 36011. Control signals, statusbits, enable information, set and reset conditions, and so forth arecommunicated between PMU controller 3100 and DSP 3600 via bus 31002.Data from measurement processor 3500 (FIG. 17) on multiple lead 35001and information for processor 3500 on lead 36002 link processor 3500 andDSP 3600. Bus 36001 originating from DSP 3600 carries system reset andenable signals controlling event monitors within DSP 3600.

2.2.3d PMU Controller

PMU controller 3100 is a microcomputer-based system also running underthe same operating system (OS) as DCN 140, LTS controller 2000 and portcontroller 2200. In PMU controller 3100, the tasks are as follows:.

(a) PARALLEL DATA task controls the transmission and reception ofmessages over parallel-oriented bus 20001 shown in FIG. 11. A message isreceived by PMU controller 3100 on an interrupt driven, byte-by-bytebasis. When a full message has been received, OS runs the PARALLEL DATAtask to determine where the buffer memory storing the message is to besent for processing. The PARALLEL DATA task also formats full buffersfor transmission UP to LTS controller 2000. The PARALLEL DATA task issimilar to PARALLEL OUTPUT task 11407 of FIG. 7 associated with DCN 140.

(b) ADMINISTRATION task runs several diagnostic functions, including thehandling of illegal instruction traps from system malfunctions andperiodic software checks on critical, RAM-stored tables. This checkingis implemented as a cyclical redundancy check and is performed in lieuof hardware parity checking.

(c) DUMP MEM task arranges for transmission of blocks of memory to LTScontroller 2000 upon request or upon detection of an error condition inthe circuitry of PMU 2101.

(d) PMU task configures and energizes the circuitry of PMU 2101,collects data and formats the data for transmission UP the hierarchy.The particulars of this task are now discussed with reference to thetests defined in Section 2.2.1c and in view of FIGS. 25 and 26.

The PMU task, represented by element 3101001 in FIG. 25, receives bufferinformation as transmitted by the PARALLEL DATA task. Entries in thebuffer specify which test is to be performed. The data specifies whichof the many possible test requests summarized in Section 2.2.1c is to beselected; three such requests, depicted by elements 3101002-3101004 inFIG. 25, include AC3TY, OCFEMF and CN₋₋ GRFV. In each case, control ispassed to measurement cycle controller 3101005, which is a softwareroutine that causes the same basic functions to be performed each time,regardless of the particular test request. The functions differ only intheir handling and formatting of the data returned by DSP 3600.

Measurement cycle controller 3101005 provides direct control of PMUcircuitry as depicted in the structure chart of FIG. 26. The software ofcontroller 3101005 operates sequentially from left-to-right andtop-to-bottom in FIG. 26. Each test request (3101002-3101004 of FIG. 25)calls this softeware as many times as is necessary to obtain therequired measured currents on the loop under test. For instance, theOCFEMF test request requires cycle controller 3101005 to operate threedifferent times with a different circuit configuration each time. Theoperation of cycle controller 3101005 for each repetition is set forthin the following with reference to FIG. 26.

First, a so-called primitive table, stored in ROM of PMU controller3100, is copied into a RAM copyspace via routine 3101010. Each testrequest is completely specified by its primitive table. Parametersspecified in the table include: settings for various system relays thatconfigure, for example, routing of TIP and RING through the apertures ofthe magnetic current sensing cores; the type of signal to be measured(AC or DC); the DSP filtering algorithm that is to process measureddata; and the reference frequency to be used for synchronousdemodulation. In fact, approximately forty bytes of memory are needed tocompletely specify each PMU test request. In addition, a dedicatedmemory area is established into which variable data parameters specifiedin the buffer sent from LTS controller 2000 may be stored. Thesevariable parameters typically replace default parameters built into eachprimitive table. Thus, if the primitive table has been defined to allowmodification, routine 3101011 transfers the data from the dedicatedmemory area and makes the appropriate changes, if any. The AC and DCsource generators comprising circuit 3200 are deenergized to guaranteethat overloads do not cause PMU failures as the PMU configuration ischanged. Likewise, a delay routine is entered after all relays aretransferred to a quiescent state to allow for energy dissipation.

Next, in preparation for the application of AC voltage to the loop undertest, dissipation resistors within source drivers 3301 ad 3302 areselected and applied to preclude voltage-overload failures. Then theentries in the primitive table corresponding to memory-mappedperipherals are sequentially written into memory by routine 3101016; inparticular, the writes energize PMU relays to establish the variousmeasurement paths required of the present test request. AC and DC sourcegenerators within circuit 3200 are then enabled by the next tworoutines. The application of the test signal to the loop is now completeand the remaining routines in measurement cycle controller 3101005 focuson collecting the measured data.

The various channels through detector 3400 and measurment controller3500 utilized in processing detected currents each have differentresponses to applied signals. At system start-up these responses aremeasured and stored as "calibrate" values. When a loop is measured, thecalibrate values of the channels must be taken into account. The routinelabelled 3101019 retrieves the values from memory and copies thesefactors for the channels into an array where they may be easilyreferenced in order to adjust the measured signals. In addition, routine3101020 initializes pseudo-gains which likewise must be accounted forwhen the final detected current values are calculated.

Next, routine 3101021 downloads the required processing program into DSP3600. The downloading occurs in three steps. First, after the basicprocessing program is downloaded, measurement channel offsets are copiedinto an array from memory for ready reference. The offset correction issimilar to the calibrate value adjustment in that offsets will be usedto convert actual measurements into corrected measurements. However,offset correction occurs via a subtraction operation whereas calibratefactor adjustment is via multiplication. The second step involvesexamining the primitive table to determine if any parameters in thebasic processing program are to be modified, such as current thresholds.If so, the third step makes the required changes in primitive tablevalues via routine 3101025.

The penultimate routine 3101022 runs the measurement cycle. The samplerate passed to measurement controller 3500 operates a system measurementtimer. The rate is determined by a number of factors, including thedigital filter to be used in DSP 3600 and the number of channels to bemeasured. This run cycle continues until the digital filter settles, thetest times out or an interrupt occurs. Assuming a successful completion,routine 3101022 collects the measured current data from DSP 3600 andmakes required adjustments. Finally, routine 3101026 resets PMU 2101,thereby completing the measurement cycle.

Control of the circuitry of PMU 2101 then passes to the test requestroutine of FIG. 25 overseeing the test run. Depending upon the stage ofoperation, reconfiguration may be initiated to collect additional dataor the collected data may be transmitted to LTS controller 2000.

As indicated in the above discussion, calibration is an important partof the overall operation of PMU 2101. Besides the three calibrationprocedures already identified, that is, (a) offset correction onmagnetic current sensor cores, (b) gain factor values determined fromapplying known, high level signals and measuring responses and (c) DCoffsets determined from responses without any input signals, one othercalibration procedure is utilized. Oftentimes, the precise values of thereal and imaginary parts of the loop admittance provide valuable faultdiagnosing information. To obtain these values, it is necessary tocorrect for phase offsets within subsystems 3300, 3400 and 3500. Phaseoffsets are determined by a three-step process. First, a terminationwithin element 3310 of FIG. 20 having a known phase shift at thefrequency of interest is applied across the TIP and RING leads. Then theactual phase shift is measured. By comparing the expected phase shift tothe measured phase shift, the phase shift through the various channelsmay be determined. Digital signal generator 3200 may then compensate forthe individual phase shifts by selecting appropriate table values fromthe ±cos θ tables as the starting points during signal generation.

2.2.4 LTS Circuits for Establishing Loop Connections

To describe the functions of the remaining LTS circuits of FIG. 11 notexplicitly referenced or discussed in some detail to this point, atypical sequence of operations involving most of these circuits isdescribed. Variations on the sequencing presented are also identifiedwhere appropriate, and others may then be readily identified by thoseskilled in the art in view of the foregoing discussion. The circuits tobe discussed include talk circuits 2301-2306, DDD circuit 2400, ringingdistributor 2500, busy/speech detector 2600, trunk dialer 2650,equipment access network 2700, ports 2801-2816, sleeve lead control unit2950 and tracing tone source 2900. The operations to be discussedindicate how a talk circuit is established between a Maintenance Centeradministrator and a customer.

Access to the customer's loop through EAN 2700 commences with thetransmission of the access request from LTS controller 2000 to portcontroller 2200, as elaborated upon in the preceding sections,particularly Section 2.2.1a. As a first step in the sequence, portcontroller 2200 selects, from among the sixteen ports 2801-2816, a freeport having a test trunk 9401, . . . , or 9416, and a correspondingsleeve lead 9417, . . . , or 9432, associated with the telephone numberof the customer's loop. (Trunk groups in a central office environmentare associated with a subset of the set of accessible telephone numbers.Thus, another accessing possibility is that of having a switchingarrangement to connect any port to a trunk from the trunk groupservicing the desired telephone number. This adds another degree offreedom, but one that is not essential to the immediate discussion.) Forthe sake of clarity of presentation, it is presumed that port 2801,trunk pair 9401 and sleeve lead 9417 satisfy the request. Assuming alsothat the selected trunk pair does not exhibit hazardous voltages, thenext step is to connect trunk dialer 2650 through EAN 2700 to port 2801.To understand the technique for accomplishing this, reference is made toFIG. 27.

As depicted in FIG. 27, EAN 2700 is comprised of an array of 4×6 switchmatrices 2710-2713. Focusing on matrix 2710, four horizontal leads28010, . . . , 28040 originate from ports 2801-2804, respectively; eachlead actually represents both the TIP and RING served by thecorresponding port. The six vertical leads, also representing a pair ofconductors, connect to the following six elements: PMU 2101; tracingtone source 2900; talk circuit 2801; the dial pulsing (DP) portion oftrunk dialer 2650; the multifrequency (MF) dialing portion of dialer2650; and busy/speech detector 2600. The three leftmost vertical leadsare controlled by L control section 2701 of EAN 2700, and each leadforms one lead of a unique, switchable crosspoint (L1-L3 for the firstvertical lead, L4-L6 for the second, and so forth), the other lead ineach case being provided by one of the four horizontal leads. Similarly,P control section 2702 operates crosspoints P1-P2 in matrix 2710. AsFIG. 27 depicts, EAN 2700 is modular and may be expanded vertically toinclude more ports or horizontally to include more elements such asprecision measurements units, talk circuits and busy/speech detectors.The main limitation on the expansion characteristics is set by constantsfixed within the software design; these constants are derived frommemory considerations, timing constraints and throughput rate.

Continuing with the example, it is supposed that dial pulses must beapplied to trunk 9401 for proper operation; this information istypically stored in the memory section of port controller 2200. Pcontrol section 2702 then closes switch point P1 in matrix 2710 toaccess the dial pulsing portion of dialer 2650. A signal, typically alow impedance placed metallically across the trunk pair by dialer 2650,notifies the office switch that dialing is planned. The office equipmentresponds, usually with a TIP-RING reversal, to acknowledge the requestand then manipulates the sleeve lead; the type of manipulation dependson the central office type. For instance, with one office type,providing a high sleeve current seizes trunk 9401 and prepares it toaccept dial pulses. Concurrent with sleeve lead manipulation, portcontroller 2200 loads dialer 2650, via bus 22001, with the telephonenumber upon reception of the TIP-RING reversal; once loaded, dialingcommences. At the completion of dialing, another TIP-RING reversaleffected by the circuitry of trunk 9401 indicates that the customer'sloop is now accessed in a bridging or monitor mode.

Since it is possible that the subscriber is utilizing the loop,crosspoint P2 is opened to disconnect dialer 2650 and crosspoint P3 isclosed to attach busy/speech detector 2600. Two basic tests areperformed by detector 2600. First, the loop is checked for DC voltae onthe TIP and RING. If a loop is found to be DC busy, speech detection isperformed by monitoring the line for bursts of energy that arecharacteristic of speech. The status of the loop is returned to portcontroller 2200. If it is presumed that the loop is idle, LTS controller2000 is notified that port access is complete and detector 2600 isdisconnected. In addition, trunk parameters determined as systemcalibration, including trunk type, length and resistance, are returnedwith the response message.

Since a customer-administrator connection involves a callback mode ofoperation, an access utilizing an idle talk circuit 2301, . . . , or2306 is progressing concurrently with port access. LTS controller 2000commences this access directly via bus 20002. Presuming talk circuit2301 is the idle talk circuit seized, the DDD dialer circuit 2400 isconnected to talk circuit 2301 via channel 20003. Talk circuit 2301 thendraws dial tone over one of the DDD pairs comprising cable 23011 byplacing a low impedance across the pair. DDD dialer 2400, which wasloaded with the callback digits when it was allocated, now dials oroutpulses the number of the telephone to be used by the maintenanceadministrator. When the administrator answers the call, the "0" digit(KEY ZERO) on the multifrequency pad is pushed; in turn, talk circuit2301 detects the frequencies assigned to the "0" digit and LTScontroller 2000 is signalled accordingly. LTS controller 2000 indicatesto L control section 2701 that crosspoint L3 is to be closed, therebyinterconnecting port 2801 with talk circuit 2301 (presuming loop accessis completed).

The customer may now be contacted, and this is accomplished by LTScontroller 2000 sending appropriate information to ringing distributor2500, such as the particular talk circuit that requires ringing and thetype ofringing (single party, two-party, and so forth). Ringing isapplied, in this case, through talk circuit 2301 by ringing distributor2500. Customer acknowledgment of the ringing, typically by the receivergoing off-hook, trips ringing distributor 2500. Talking battery issupplied to the loop by talk circuit 2301 since a no-test trunk normallydoes not supply DC to the loop.

At this point in the description, the desired customer-administratorcontact has been achieved. To carry the example a few steps further, itmay be that the customer is asked to dial a certain digit so that a dialpulse analysis may be effected. The crosspoint L1 would be closed toconnect PMU 2101 to port 2801 and crosspoint L3 would be opened for theduration of the test.

If a craftsperson is engaged in loop testing at a field location, it mayhave been the craftsperson that was contacted by the above procedure,rather than a customer. If the craftsperson requires a tracing tone, sayfor TIP-RING identification, crosspoint L2 is switched and tone source2900 is now connected to the loop. Tone is applied from source 2900, andnot PMU 2101, since a tone usually is required for an extended durationand it is inefficient to relegate PMU 2101 to a low-level operation.

Once the tone is applied, the ACCESS/TEST task of port controller 2200continues to monitor the status of the loop. When the craftspersonlocates the loop having the tone applied, a disconnect signal can begenerated by a TIP-RING shorting operation performed by thatcraftsperson. The monitoring task detects this state change and sends a"status changed" message UP the hierarchy. However, the tone ismaintained until another message is received to either DROP theconnection or until a timeout occurs. The status changed messagenotifies the maintenance administrator of the on-going field activityand alerts the administrator that other test activity may beforthcoming.

2.3 Front End (FE) System

The description to this point has focused, primarily, on thecapabilities of DCN 140 and LTS's 160,161 with the MLT system framework.One important subsystem, namely, the FE system, including FE computers220,221 and user interface devices 230,231, requires elaboration. Thisaspect of the description focuses on how to access and utilize thesystem capabilities described in the foregoing sections.

The MLT system must provide operational data to at least two types ofusers: Repair Service Attendants (RSA), who are in contact with thecustomers, and Repair Service Bureau (RSB) personnel, who analyzetroubles and dispatch repair craft. The needs of these two users aresimilar, but not identical.

The RSA requires access and test requests with rapid responses and atest summary that provides insight to the reported trouble in a globalway. For example, is a trouble confirmed? Is it a central officetrouble, a loop trouble, a station trouble? The test should be performedautomatically when the trouble report is taken and the results areneeded promptly so that an appropriate repair commitment may be providedto the customer.

The RSB needs detailed test results and the ability to perform tests ondemand, sometimes while the repair craft is at the location of thetrouble. Thus, the RSB needs a menu of tests, some designed to duplicatethe tests performed when the trouble was reported, and some tailored toprovide data on only a subset of all possible problems.

For both users, it is necessary to interpret the test results in view ofrecorded office, loop and station or customer equipment, as extractedfrom storage computer 200, and to be somewhat tolerant of incorrect orabsent record data.

These diverse user requirements are satisfied by FE software that can bedivided into basically three categories: a terminal interface process; atest interface process; and a test supervision and control process.These processes appear in each FE computer 220,221 and are partitionedso that MLT related (DOWN) software communicates with data base (UP)software across an interface boundary, as illustrated pictorially inFIG. 1.

The terminal interface process receives test transactions from userterminals 230,231, performs data validation, formats processing requestsand forwards those requests to the test interface process on the FEcomputer actually containing the particular line record data. If theline record data is not on the same FE computer the user is connectedto, the request is forwarded via high speed parallel communications link210 to the appropriate FE computer. This arrangement is importantbecause it enables organization of loop maintenance operations in amanner that is reasonably independent of how the FE computers areorganized.

The test interface process obtains the line record data from the FEcomputer storage. The line record data and the original request data areforwarded to the test supervision and control process on the FE computerchosen to perform the test, that is, either the FE now containing theline record data or the FE to which the user is connected. When therequested tests and analysis are completed, the results are forwarded tothe terminal interface process where they are formatted and presented inthe user.

In order to enable the user to input data and receive output in auniform manner, several types of so-called masks may be called into viewof user device 230,231, typically a cathode ray tube (CRT) display. Thedisplay below is an empty Trouble Verification (TV) mask which is usedby repair personnel for all normal testing needs in an interactivetesting mode. The asterisks indicate where a user is to make entries.

    ______________________________________                                        TV   EC*    PRTR*   REQ BY*   CB*    date, time                                                             SW:    OE:                                      TN*     L#*    CMT*    CA*           CO:                                      REQ*    TEMP(F)*   PR*     OVER*   OSP:                                                                          TERM:                                      ______________________________________                                    

The fields have the following meanings:

EC--employee code.

PRTR--results of a TV request will also be sent to the designatedprinter.

REQ BY--(Requested by) identifier for printer output.

CB--(Callback) normally a 10 digit telephone number of the telephoneaccessible to the CRT user. Many of the TV requests (for instance, RING,TALK and so forth to be set forth below) require a connection betweenthis callback number and the customer's telephone equipment number;pressing KEY-ZERO ("0" on the keypad) acknowledges the answer to thecallback.

TN--(Telephone Number) normally the entry in the TN field is the numberof the equipment terminating the loop for which no-test access isrequired. However, it can also be used to specify the particular MDFtrunk group for MDF access.

REQ--(Request) any valid TV request is entered into this field; if thisfield is blank, the last entry is used as the current one.

CA--(Cable) an optional entry that is useful for documenting the mask.An entry does not change the line record information. This field istypically employed whenever it is believed the line record informationis incomplete or inaccurate and a remainder to this effect is desired,particularly on a display directed to the printer.

PR--(Pair) a field serving the same function as CA.

L#--(Line number) this entry refers to a line in the status section ofthe TV mask (discussed below). For example, if a test was run ontelephone number 362-5111, this number might be displayed as line 1 inthe status section. To test 362-5111 again, a "1" may be entered in thisfield instead of typing the full phone number. A L# always overrides aTN entry.

CMT--(Comment) seven alphanumeric characters may be entered for displayon the status section of the mask associated with the telephone number.A typical entry might be the repairperson's name that is working on aloop fault.

TEMP(F)--(Temperature-Fahrenheit) an entry is made here when resistivefault locating with LOC1 and LOC2 requests described below.

OVER--(Override) certain line record data can be ignored during testing,as follows: C overrides CO equipment; O overrides outside plant (OSP)equipment; T overrides termination (TERM) equipment; P overrides serviceprotection (SP) records; Y overrides all records. Moreover, there is thepossibility of substituting equipment for CO, OSP and TERM line recorddata. Substitution is accomplished by entering one of the following inOVER field: C#, O# or T#. For example, an "054" in the OVER fieldindicates an outside plant repeater (specifically an E6 repeater) isplaced at the CO end of the loop. These override options onlytemporarily change the line record data for a single request; nopermanent alteration occurs.

After the fields are filled with the appropriate entries, the TV requestmask is transmitted, that is, sent to the associated FE computer forprocessing. For a request that keeps access to a subscriber loop, thefollowing information is returned.

1. User entry area--The telephone number remains in the TN area, and allothers are blank.

2. A line record area--The extracted line record data is summarized onthe display.

The line record information is entered into the area shown by SW, OE,CO, OSP and TERM in the TV mask displayed above, presuming a 10 digitnumber in the TN field. The CO, OSP and TERM fields have been describedabove with respect to OVER. SW(Switch) refers to the CO switchingequipment type. The possibilities include: SXS (Step-by-step); XBAR-1and XBAR-5 (Crossbar offices); ESS-1, ESS-2, ESS-3, ESS-5 (Electronicswitching offices); PANEL; and DMS10 (Digital switch). OE (Originatingequipment) refers to the location of the subscriber loop at the switch.

The entries of the CO, OSP and TERM areas are especially importantbecause the equipment they represent influence the outcome of the MLTsystem tests. Whenever a test is made on a line with special equipmenton it, that equipment is taken into account when analyzing results. Forexample, if a test is effected on a loop that has a Loop SignalingExtender, a DC resistance TIP-to-RING of 90K ohms or higher is expected.Normally, a value of resistance this low would indicate a TIP-RINGshort, and this would be reported to the user via a results section(described below). In this situation, however, the message reports agood loop given the special equipment. The entry LOOP SIG EXTENDER isentered in the CO area to explain why the DC resistance in the detailedresults section is low. Because of this capability, the MLT systemalgorithms are considered to be adaptive to nature in that testsignatures of numerous equipment types and locations are accounted forduring testing and presentation of output information to the user.

3. Status section--This section provides new data on the display and itappears only if at least one telephone number is presently beingaccessed. The information is shown as a numbered line under theseheadings:

    ______________________________________                                        TN   MDF     STATUS   CB   TIME  FR   CA/PR  CMT                              ______________________________________                                    

The headings have the following definitions:

TN--(Telephone Number) as filled-in by the user in making the request.

MDF--(Main Distributing Frame) upon a MDF access to a trunk, the numberidentifying the trunk to the frame attendant is returned.

STATUS--some TV requests remain on a loop for a prolonged period, but donot require a callback path. They stay on the loop for a predeterminedperiod or until removed by the user. One of the following entries isreturned: TONE or TONE+ if that request was made; 1SIDED or 2SIDED if aLOC request was entered and the bad pair has a one-sided or two-sidedresistive fault, respectively; GOODPR or REFPR if a request of the typeLOCGP is made and a good pair or marginally good pair is located,respectively; (blank) for all other TV requests.

CB--(Callback) on a callback between a subscriber's telephone number andthe administrator or user's test position, a remainder is returned toindicate a long-term connection is maintained and the request whichestablished the connection. For instance, such entries as TALK for aTALK or RING request or MON for a MON request or a RING request to abusy loop are possible entries.

TIME--the number of minutes elapsed since loop access is displayed, orif TONE is requested, the number of minutes since the tone has beenapplied is shown.

FR--(Frame) the telephone number of the frame serving the number placedin the TV area.

CA/PR--(Cable/Pair) reflects information entered by the user prior totransmission of TV request.

CMT--(Comment) the comment entered on the last request to this statusline is displayed.

The status section can hold up to five accesses at a time. Dropping of aloop access causes an automatic renumbering of status lines followingthe dropped loop.

4. Results section--The results of the particular TV request aredisplayed. The testing accomplished by the MLT system varies as afunction of the request. The requests may be classified and brieflydescribed as follows:

    ______________________________________                                        (a) Information Requests                                                      HELP    Provides a list of all TV requests                                    (REQ) ? Provides a description of whatever                                            request is substituted for REQ                                        INFO    Provides general information such as                                          frame phone numbers, assignment                                               phone numbers, and so forth                                           TR(#)   Permits transfer of work between user devices                         (b) MDF Requests                                                              MDF     Access an MDF trunk for subsequent requests                           MDF(GR) Access a trunk from a certain MDF trunk group                         MDF (#) Access a specific MDF trunk                                           (c) Test Requests                                                             FULL    Performs a standard test series on                                            inside and outside portions of the loop                               LOOP    Performs the standard test series                                             on the outside portion only                                           CO      Performs tests on the Central Office                                  Quick   Performs a quick test series that measures                                    AC and DC characteristics and loop length                             RINGER  Identifies the number and configuration                                       of standard ringers on the loop                                       SOAK    Identifies swinging resistance conditions                             (d) Callback Requests                                                         RING    Ring a line                                                           R(#)    Ring a specific party on a multiparty line                            T       Talk over the subscriber's loop                                       MON     Monitor a subscriber's loop                                           CALL    Make a call using the subscriber's line circuit                       (e) Subscriber Interaction Requests                                           DIAL    Test a subscriber's rotary dial                                       REV     Identify in-band signaling instrument                                         for polarity reversals                                                TT      Test subsciber's in-band signaling pad                                (f) Craft Interaction Requests                                                TONE    Places a metallic tone on a loop                                              for pair identification                                               TONE+   Same as TONE with increased amplitude tone                            TONECA  Places a tone longitudinally on loop                                  LOOK    Monitor for an intentional fault                                      LOCATE  Initiates the resistive fault                                                 measurement strategy; recommends                                              single-or double-sided procedure                                      LOC1    Determines distance to a single-sided fault                           LOC2    Determines distance to a double-sided fault                           LOCGP   Verfies the condition of a good pair                                          for double-sided fault detection                                      (g) Drop/Keep Access Requests                                                 X       Drop all testing equipment from loop                                  XCB     Drop a callback path                                                  XTONE   Drop a tone from a loop                                               KEEP    Extend timeout of a no-test or MDF trunk access                       (h) Coin Requests                                                             COIN    Perform a FULL test series on a coin loop                             CSET    Check totalizer and relay in coin set                                 CHOME   Home coin totalizer                                                   CCOL    Operate coin relay to collect coins                                   CRET    Operate coin relay to return coins                                    LRM     Measure loop resistance of coin loop                                  GRM     Measure ground resistance of coin loop                                ______________________________________                                    

Rather than describing each of the requests in detail, one request isselected as exemplary and the user-request interaction is discussedbelow. Applicability of this description to the other TV requests,particularly in view of the high-level language program listingspresented later, will be apparent to one possessing ordinary skill inthe art.

The particular request chosen to exemplify the TV requests is the FULLtest request. This test request provides a series of tests tocomprehensively analyze the entire telephone loop of a particularsubscriber. It provides detailed results and a summary of the conditionof both the inside (central office) and outside portions of the loopunder test. The following tests, briefly described in Section 2.2.1c,are completed: OCFEMF, DC3TY, AC3TY, BAL, THERM, DTA, SOAK, RCNT andROH₋₋ TEST.

The display for the FULL request including the status and resultssection, has the following format:

    ______________________________________                                        TV  EC     PRTR     REQ BY CB   date,time                                     TN     MDF     STATUS   CB   TIME  FR   CA/PR CMT                             1.  9995559898         0     555-7432                                                                             534-7611                                  TN  9995559898      SW:SXS OE:8829-128                                        REQ   L#     CMT     CA      CO:                                              TEMP(F)      PR        OSP:                                                   FULL               TERM:SIN. PARTY                                            VER. 22: HARD SHORT T-R                                                       CRAFT: DC SIG.                                                                             MLT:DC SIG.    AC SIG.                                           KOHMS   VOLTS    KOHMS     VOLTS  KOHMS                                       ______________________________________                                        7         T-R    7.76        T-R   10     T-R                                 1750    0 T-G    3500      0 T-G  550     T-R                                 1750    0 R-G    3500      0 R-G  560     R-G                                 ______________________________________                                        CENTRAL OFFICE                                                                LINE CKT   OK                                                                 DIAL TONE  OK                                                                 ______________________________________                                    

The newly appended areas form the results section. In this section, itis indicated that there is a short on the loop. This conclusion ispresented with the aid of a VER (verification) code number (22 is thiscase) and the summary message HARD SHORT. The MLT system has numerousVER codes and summary messages available for selection and display tohelp in diagnosing any trouble. Besides the brief summary area, adetailed results area displays all the test results. Here, a low T-R DCresistance value of about 7k ohms caused the HARD SHORT diagnosis. TheT-G and R-G DC resistance values are high so there is no groundcondition. The AC signature is typical of a standard telephone providingthe end-of-line termination, so no fault condition is detected by the ACportion of the test. All DC and AC voltages are zero indicating thatthere is not a cross with another voltage source. Finally, the centraloffice equipment is not faulted. No loop length, balance or ringerinformation is displayed since accurate results cannot be produced for ashorted line (or other faults which mask the tests). If these values aredisplayed, they would appear in the area to the right of the CENTRALOFFICE area.

3. MLT CIRCUITRY AND PROGRAMS

3.1 DCN Implementation

3.1.1 Circuitry

With reference to FIG. 28, tier 1 device 1401 (FIG. 3), which is alsorepresentative of devices 1402-1412, comprises basically two networks,namely, the CPU circuitry of FIG. 29 and the I/O circuitry of FIG. 30.In fact, as indicated by the block diagrams relating to tier 2 and tier3 in FIG. 28, the CPU circuitry of FIG. 29 is general purposemicrocomputer circuitry used by all three tiers of DCN 140.

Referring now to FIG. 29, CPU 500 is composed of: reset circuit 501;interrupt circuit 510 having 24 vectored priority interrupts; addressbuffer 520; address decoder 530 providing 32 decoded chip-selectsignals; RAM 540 providing 16K bytes of static memory; processor 550containing the microcomputer; and system timer, buffer and circuitidentifier 570. Illustrative embodiments of these circuits as well astheir interconnections will be described below.

As a preliminary, it is important to note that the bus designated IBA isan internal bus having paths that both originate from and terminate oncircuits comprising FIG. 29. On the other hand, a bus prefaced with an`EB`, for example, bus EBA, is a bus having path originations orterminations external to the circuits of FIG. 29. In addition, a signalin capital letters followed by an asterisk (e. g., RESET1*) indicatesthat a low TTL level activates the corresponding function.

The first circuit considered is reset circuit 501; its circuit detailsare shown in FIG. 34. Reset circuit 501 disables, via RESET1* lead,processor 550 until DC supplies 502 and 503 are within operating limits;supply levels are sensed by the cascade combination of NAND circuit 504,one-short multivibrator 505 and NOR gate 506. Once the voltageconditions are met, one-shot 505 maintains the disable condition for anadditional 5 to 10 sec. interval before allowing an enable condition.Processor 550 is then disabled upon occurrence of: (i) loss of supplies502 or 503; (ii) a manually generated reset signal transmitted by Dflip-flop 509 and NOR gate 508 from the PB* lead, or (iii) a signal onthe TIMEOUT lead, propagated by NOR gates 507 and 508, indicating, forexample, a hardware failure or a software loop. The origin of theTIMEOUT inhibit (TOINH) feeding gate 507 is discussed below.

The circuitry of interrupt controller 510 is shown in FIG. 35. ThreeAdvanced Micro Devices AM9519A priority interrupt controllers (PIC)511-513, each of which provides eight interrupts, form the basis of theimplementation. Each controller is programmed via the I/ORD* and I/OWR*leads as well as CS7*, CS1* and CS2*, respectively. When one or moreinterrupt requests IR0-IR7, IR10-IR17 or IR20-IR26 appear at the inputsto one or more PIC's, the GINT* signal is pulled low, requesting aninterrupt from processor 550. When processor 550 acknowledges theinterrupt, it issues a read from a predetermined memory location whichcauses the IVR* lead to be pulled low. In response to IVR*, each PICholds its PAUSE* lead low for up to three cycles to determine which PIChas the highest priority. Finally, the PIC that services the highestpriority interrupt will output the interrupt vector byte, on leadsD0-D7, and release the PAUSE* lead.

Processor 550, depicted in FIG. 36, comprises: microprocessor device551, with its associated clock 553 and timing generator device 555; databuffer 552; and RDY (ready) line circuit incorporating devices 556-559.

Microprocessor 551 is, in the preferred embodiment, a BELLMAC-8microprocessor furnished by the Western Electric Company. (BELLMAC is atrademark of the Western Electric Company). Device 551 is describedbasically in the article entitled "MAC-8: A Microprocessor ForTelecommunications Applications", The Western Electric Engineer, at page41 et seg., July 1977 by Herbert H. Winfield. From this article, thebasic architecture and operational characteristics of device 551 may bededuced.

For instance, it is evident that microprocessor 551 is a 40-pin devicehaving an 8-bit data bus and a 16-bit address bus so the addressablememory space is 64K bytes, that RAM and ROM are provided externally andthat a portion of RAM contains user-defined registers. Moreover, device551 comprises five major circuit blocks: an address arithmetic unit; anarithmetic logic unit; an arithmetic unit control array; an instructioncontrol logic array; and an internal register array having a programcounter, a stack pointer and a condition register. Other device detailsnecessary to teach one skilled in the art the subject matter of thepresent invention will be provided as the description proceeds. To thisend, the following describes the function of and timing on theexternally accessible ports depicted in FIG. 36 for device 551;

(1) A0-A15 (Input/Output 3-State Address Bus)--For a typical bus loadingof 20 pf, the address is valid 60 ns after the start of each cycle. Thisis depicted in FIG. 37 as time TA on the line labeled ADDRESS; the clockcycle is started when the CLKOUT signal makes a high-to-low transition.

(2) CLKIN, CLKOUT--Device 551 utilizes either an internal clockgenerator or an external clock applied to the CLKIN port. CLKOUTprovides a clock output signal corresponding to CLKIN for externaldevice timing. At the highest operating rate, the time labeled TI on theCLKIN line is about 250 ns; correspondingly, time TO of CLKOUT rangesbetween (TI+10) ns and (TI+110) ns. The delay between the clocks, shownas TC, does not exceed about 200 ns. Clock 553 in FIG. 36 provides a 2MHz square-wave TTL level signal which is converted to the levelrequired by CLKIN of device 551 via inverter 554 and its associatedpull-out resistor.

(3) D0-D7 (Input/Output 3State Data Bus)-- This 8-bit bus is used formemory or I/O transfers. The MERD* (memory read), MEWR* (memory write)and RDY (data ready) ports control such transfers. Data bits on theexternal bus EBA, which are buffered by buffer transceiver 552, an 8304furnished by National Semiconductor, are strobed into an internal latchat the end of a read cycle. In a write cycle, the bus data is valid atmid-cycle. The RDY signal must be at a high logic level when checked atmid-cycle for a data transfer to occur on a MERD* or MEWR* operation.The time labeled TRD on the line shown as MERD* in FIG. 37 representsthe maximum delay time in read cycle transistions, this is typically 85ns. A similar time for MEWR* is shown as time interval TWD on the MEWR*diagram; TWD ranges between about 50 and 220 ns. The time perioddesignated TDR on the DATA (READ) line indicates the time allocated foran external memory access to prepare the data for a read operation andis typically (2TI-100) ns. Similarly, the time shown as TDN on the DATA(WRITE) line indicates the delay to stabilize data for a write operationand this time is not in excess of 235 ns. The time available for anexternal memory write is shown as TMW and this period is always greaterthan (2TI-290) ns. The interval shown as TWC depicts the time betweenwhen CLKOUT goes high and the data is valid for a write operation; thisinterval is always positive. Three trailing-edge time intervals, namely,TDRE, TWE and TDWE, associated with DATA (READ), MEWR* and DATA (WRITE),respectively, have the following specifications: (i) TDRE≧0 ns; (ii) 5ns≦TWE≦125 ns; and (iii) TDWE≧15 ns. Regarding the RDY line of FIG. 37,the time TAC, denoting the time allowed for a data ready input, is neverless than (TI-100) ns, and the time shown as TH, denoting the hold timeafter CLKOUT goes high, is always positive.

With respect to the RDY port, this port is polled at mid-cycle. If thesignal supplied by the answering device is ready for data transfer on aMERD* or MEWR* operation, indicated by a high logic level, the MERD* orMEWR* pulse terminates at the end of the cycle. On the other hand, ifRDY is low, the MWRD* or MEWR* signal remains active until the nextmid-cycle check when the process is repeated.

(4) INTREQ*--A low logic level signal input at this port indicates thatan external device is requesting an interrupt. The INTREQ* port ispolled during the last clock cycle of each instruction cycle. Therequest is accepted whenever the interrupt enable is set. To acknowledgethe interrupt, the interrupt enable is cleared, certain registers aresaved, and memory location 0xFFFF is addressed. Then the data byte 0xdd,which the interrupting device supplies, is read; this byte is used toform the interrupt vector 0x00dd pointing to the low (0 through 255)bytes in memory. Referring now to FIG. 37, the time interval TQ on theline labeled INTREQ* indicates the interrupt setup time, which may notexceed 80 ns. The hold time TQH depicted on the same line is a minimumof 200 ns.

The RESET* request has a pulse shape and time durations similar to thatrequired for an INTREQ*. A low level causes device 551 to be reset. ARESET* request is acknowledged by a request for a read of data ataddress 0xFFFF. After clearing various internal counters and clearingthe RESET* request, instruction execution starts at location 0x0000.

(5) DMAREQ* and DMAACK*--An active DMAREQ* lead indicates that anexternal device requires the data bus for a DMA operation. The DMAREQ*port is polled at the end of each clock cycle to determine if an activestate has been established. If the port is low and RDY is high, that is,device 551 is not in the so-called wait state, then DMAACK* becomesactive at the beginning of the next internal cycle. This acknowledgementpasses master bus control to the requesting device and the address bus,data bus and control leads are raised to the high-impedance tri-statemode. Again with reference to FIG. 37, the times denoted TMS and TMH onthe line labeled DMAREQ* indicate the request setup and hold times andare such that TMS≦200 ns and TMH is nonnegative. In addition, the timeperiods called TKB and TKE on the DMAACK* line represent on and offacknowledge delays, respectively. Both are less than about 100 ns.Finally, the four time durations designated TSD (on the ADDRESS line),TSB, TSE and TSF represent, respectively; the transition time betweenCLKOUT and low ADDRESS (TSD≧0); ADDRESS bus delay to achieve off and onlow-impedance modes (TSB≦160 ns and TSE≦160 ns); and beginning of floator high impedance mode on ADDRESS bus (TST≧0 ns).

The above information about signals required by or produced by device551 at its ports is now incorporated into the description of thecircuitry of FIG. 36. In particular, timing generator 555, a 129CYdevice furnished by the Western Electric Company, provides severalsupport functions for device 551, including: wait-state generation;provisioning of the RDY lead so that it remains active during a systemreset; generation of the peripheral control signals I/ORD* and I/OWR*;and decoding of the interrupt-acknowledge signal IVR*. Device 555permits device 551 of the preferred embodiment to be used with a varietyof other commercially available I/O devices which typically are notadapted to utilize the raw signals from the BELLMAC-8 microprocessor.

As indicated earlier, the RDY signal causes device 551 to go into a waitstate when low. There are three events which require wait states,namely, interrupt acknowledge cycles, peripheral I/O cycles and thefirst memory cycle after a DMA transfer. The wait state during interruptacknowledge occurs when PIC's 511-513 pull down their PAUSE* leads. Thissignal is propagated through gate arrangement 538 (FIG. 40) to NAND gate558 and inverter 557 to the RDY port. Gate arrangement 538 of FIG. 40prevents PIC's 511-513 from causing a wait-state during reset.(Moreover, gate arrangement 537 and D flip-flop 536 of FIG. 40 insure await-state does not occur until software initialization generates awrite (WR*) to chip-select location 27 (CS27*)).

The wait state during peripheral I/O is generated whenever timinggenerator 555 detects an IO* signal at its WSS* port. Its RDY port isasserted low and, after inversion, is also propagated through gatearrangement 538 of FIG. 40.

The wait state during the first cycle after a DMA transfer is providedby a pulse from D flop-flop 556 and NAND gate 557 as a result of aDMAACK* acknowledge from microcomputer 551 of FIG. 35.

Focusing now on the signal provided to the RESET* port of device 551, aprocessor reset occurs whenever the RESET1* signal from reset circuit501 is received. During reset, with reference to FIG. 34, TIMEOUT isdisabled via the TOINH lead supplied to NOR gate 507. The signal onTOINH is generated by D flip-flop 536 of FIG. 40. A write (WR*) to thelocation associated with CS27* will enable TIMEOUT, and this writeshould be performed after PIC's 511-513 and programmable interval timer527 of FIG. 41 have been initialized.

With reference to address buffer 250 of FIG. 38, buffering is providedby line drivers/receivers 521 and 522, type S244 devices furnished byTexas Instruments. Address signals appearing on leads A0-A3 are latchedin bistable latch 524, a LS75 device supplied by Texas Instruments.Latching is necessary to insure low address leads remain stable at theend of the read cycle so as to insure compatibility with variousperipheral devices. The address, data and control buffers are disabledduring DMA by the AEN signal so external peripherals can assert thesignals needed for DMA. The control signals RD*, WR*, I/ORD* and I/OWR*on bus EBA are buffered by another S244 type device 523 to obtain MERD*,MEW*, XRP* and XWP*, respectively.

RAM circuit 540 of FIG. 39 has eight 2K×8 static RAM's 541-544,bidirectional buffer 547 and two fusible link bipolar PROM's 545 and546. Buffer 547 is bidirectional type LS245 supplied by TexasInstruments, whereas PROM's 545 and 546 are type 28L22 supplied by TexasInstruments and RAM's 541-544 are type 61A manufactured by the WesternElectric Co. PROM's 545-546 decode address leads A9-A15 to provide eightRAM selects, one for each 2K×8 Ram, as well as control signals LENROM*,RAM* and IO*, which indicate whether the current address is in,respectively: external memory range (0x0000-0xBFFF); RAM range(0xC000-0xFDFF); or I/O range (0xFE00-0xFFFF).

Each PROM 545 or 546 is 256 words by 8 bits. PROM 545 is programmed sothat all addresses up through 0xBF contain 0xFF. The next fifty-sixaddresses (0xCO-0xF7) are equally divided into eight address segmentscontaining, respectively: 0xFE; 0xFD; 0xFB; 0xF7; 0xEF; 0xDF; 0xBF and0xF7. The final eight address 0xF8-0xFD contain 0xF7 in the first sixlocations and 0xFF in the last two locations. PROM 546 is programmed sothat addresses 0x00-0xBF contain the hexidecimal data 05, whereasaddresses 0xC0-0xFF contain 0x09, except for address 0xFE which hasstored 0x0E. Buffer 547 is enabled by RAM* and its direction isdetermined by the RD* signal. The complete address map of the circuitryof FIG. 29, including areas asserted by the chip select signals to bediscussed next may be summarized as follows:

    ______________________________________                                        Start        End         Selected Memory                                      Address      Address     or Chip Select                                       ______________________________________                                        0 × 0000                                                                             0 × BFFF                                                                            External Memory                                      0 × C000                                                                             0 × FDFF                                                                            Internal RAM                                         0 × FE00                                                                             0 × FE0F                                                                            CS1*                                                 0 × FE10                                                                             0 × FE1F                                                                            CS2*                                                 0 × FE30                                                                             0 × FE3F                                                                            CS4*                                                 .            .           .                                                    .            .           .                                                    .            .           .                                                    0 × FF40                                                                             0 × FF4F                                                                            CS21*                                                0 × FF80                                                                             0 × FF8F                                                                            CS22*                                                .            .           .                                                    .            .           .                                                    .            .           .                                                    0 × FFE0                                                                             0 × FFEF                                                                            CS31*                                                ______________________________________                                    

FIG. 40 depicts address decoder 530 which is composed of two TexasInstruments 74LS154 one-of-sixteen selectors 531 and 532, gates 534 and535 and inverter 533, thereby providing 32 possible chip-selects. LeadsA8 and IO* determine if one of the selectors should be enabled. Ifselected, the decoders use address leads A4-A7 to determine which ofsixteen possible outputs should be asserted. The above map alsosummarizes the areas of memory enabled due to chip-select assertions.

System circuit 570 is depicted in FIG. 41 as comprising device 572,which is an Intel 8253 Programmable Interval Timer (PIT). Device 572 isprogrammed via CS5*, I/OWR* and I/ORD*. Address leads A0 and A1 accessthe registers internal to the PIT. There are three individuallyprogrammable timers within PIT 572. The first timer (OUT0) is driven byLCLK0 (which is provided as an output from processor 550 of FIG 36) andis connected to the other two timers. Timer two (OUT1) providesinterrupt lead GT to device 513 of FIG. 35 and serves as a system clockinterrupt at programmable intervals. Timer three (OUT2) is used togenerate a heartbeat timer such that if the timer is not updated by thesystem software within its programmed interval, a hardware reset willoccur. Timer 1 also provides the BAUD signal for use with externalcircuitry.

FIG. 41 also provides a circuit device 571 as a circuit identifier.Eight external leads CK0-CK7 may be interrogated under software controlto implement user-selectable options. When CS6* is asserted, device 571,which is type S244, gates the signals from leads CK0-CK7 onto D0-D7. An8304 bidirectional transceiver 573 buffers external bus signals relatingto DMA transfers, reset, ROM enable and external clock to the internalbus IBA. D flip-flop 574, when combined with flip-flop 556 of FIG. 36,quarantees a minimum of one clock cycle from the time DMAREQ* isasserted until DMAACK* is asserted.

FIG. 42 depicts the signals appearing on internal bus IBA as well asexternal busses EBA, EBB and EBC. The following table summarizes theexternal busses in terms of function and description.

    ______________________________________                                        Designation  Function   Description                                           ______________________________________                                        A0-A15       I/O        tri-state address                                                             bus bits 0-15                                         AEN*         I          address enable                                        BAUD         O          local baud rate clock                                 CK0-CK7      I          circuit identifier                                                            straps                                                CLKO         O          processor clock                                       CS4*         O          chip select                                           CS8*-CS21*   O          chip selects                                          CS25*-CS26*  O          chip selects                                          CS28*-CS31*  O          chip selects                                          D0-D7        I/O        tri-state data                                                                bus bits 0-7                                          DMAACK*      O          processor DMA                                                                 acknowledge                                           DMAREQ*      I          DMA request                                           ENROM*       O          external ROM enable                                   I/ORD*       I/O        tri state I/O read                                    I/OWR*       I/O        tri-state I/O write                                   IR00-IR07    I          interrupt requests                                    IR10-IR17    I          interrupt requests                                    IR20-IR26    I          interrupt requests                                    PB           I          manual reset button                                   RD*          I/O        tri-state read                                        RESET*       O          reset signal                                          WR*          I/O        tri-state write                                       ______________________________________                                    

With reference to FIG. 30, the second tier 1 network, namely I/O circuit600, comprises: ROM 601 providing up to 48K bytes of memory; bus circuit620 providing a GPIB talker/listener/controller (T/L/C) interface; twohigh-speed DMA circuits 630 and 640 with accompanying data buffer 635;two high-speed data link interfaces 650 and 660, and associated buffer670, implementing the synchronous data link control (SDLC) protocol; andchip selector 680.

Memory circuit 601, shown in detail in FIG. 43, accomodates six 8K×8Intel 2764-type EPROM devices 611-616. Fusible-link, bipolar PROM 602,which is a type 28L22, decodes address leads A13-A15 and produceschip-selects for each of the six devices 611-616. The following tableshows how PROM 602 is programmed (device 611 typically provides thelowest 8K byte memory segment and device 616 the highest 8K bytes):

    ______________________________________                                        A15    A14          A13    Device Enabled                                     ______________________________________                                        0      0            0      611                                                0      0            1      612                                                0      1            0      613                                                0      1            1      614                                                1      0            0      615                                                1      0            1      616                                                ______________________________________                                    

Device 603, a type LS245, isolates memory data bus 619 from data bitsD0-D7 on bus EBA. The direction of device 603 is determined by the RD*lead and is enabled when the ENROM* signal is asserted (although whenRAM* is asserted, buffer 603 may not be enabled).

The GPIB talker/listener/controller circuit 620 shown in FIG. 44comprises an Intel 8291 Talker/Listener (T/L) device 621, two GPIBbuffers 622 and 623 of the type 8293 supplied by Intel, and an Intel8292 GPIB Controller device 624. This latter device is a microcomputerthat performs standard GPIB bus control operations on the sixteen leadsDI01, DI02, . . . , DI08, DAV, . . . , NDAC appearing on bus 14101.Device 624 utilizes a two-phase 6 MHz clock generated by 12 MHz crystal625 and J-K flip-flop 626. Resistors 627 and 628 are pullup resistorsused to meet the rise-time requirements of device 624. Two types ofinterrupts are provided by device 624, namely, "task complete" and"special event", and these are sent to interrupt circuit 510 (FIG. 29)via leads IR17 and IR16, respectively. Buffer 622 is arranged to operatein IEEE standard implementation Mode 3 whereas device 623 is energizedas per Mode 2.

DMA circuits 630 and 640 of FIG. 30 allow GPIB data transfers to occurat a rate of approximately 200,000 bytes/second. The circuitryassociated with the DMA arrangements is shown in FIGS. 45 and 46; thesetwo figures should be considered in juxtaposed relation, with FIG. 45 onthe left, to properly visualize the DMA circuitry. The internal bus IBDMcouples the portion of the DMA circuitry in FIG. 45 to the remaining DMAcircuitry of FIG. 46.

Two Advanced Micro Devices AM9517A DMA controllers, shown as elements631 and 641 in FIG. 46, form the basis of the DMA implementation. Atotal of five externally accessible DMA channels are realized, two foreach SDLC data links 9201 and 9202 (SERI1 and SERI2 busses), and one forGPIB channel 14101. A sixth channel is used internally by controllers631 and 641 for alternating DMA cycles between controllers. During a DMAcycle, DMA circuits 630 and 640 (FIG. 30) cooperate to place the 16-bitsA0-A15 on the address bus. Bits A8-A15 are latched into octal latch 642,an Intel 8282 device, whereas bits A0-A7 are buffered by LS245 device632. The RD*, WR*, I/ORD* and I/OWR* leads are asserted during a DMAcycle, and LS245 latch 645 of FIG. 45 buffers these leads. The AENsignals from controllers 631 and 641 are logically OR'ed in gate 643 todetermine the propagation direction of elements 645 (DIR) 632 (DIR) and642 (OE*) as well as the control signal AEN* that disables processor 550(FIG. 29) address and data buffers. LS245 device 635 isolates theexternal data bits D0-D7 from internal bus bits LB0-LB7.

In order that DMA request signals do not coincide with the rising edgeof the clock and because GPIB device 621 asserts its request leadsynchronously, gate 633, a LS273 supplied by Texas Instruments, latchesthe request on the falling edge of the clock. Also with respect totiming, since the local AEN signal of controller 631 is asserted until aDMA cycle is finished, the local HRQ signal of controller 631 is NOR'edwith AEN in NOR gate 644 to produce an inverted, trailing edge generatedsignal for DMAREQ*.

The internal EOP* signal of controller 631 is a bidirectional "end oftransfer" signal. During output transfers of the GPIB type, when thelast byte of a message has been sent, EOP* is asserted low. The invertedversion of EOP* produces an interrupt on IRO3 of EBA. During inputtransfers of the GPIB type, the "end of transfer" signal is generated byinverter 634. This is accomplished by latching the EOI* signal generatedby GPIB circuit 620 into D type flip-flop 636 by the rising edge of theinternal DREQ signal (externally on DRQ03) of T/L device 621. When a DMAcycle is granted for GPIB circuit 620, EOP* of controller 631 is pulledlow by inverter 634, thereby disabling the GPIB channel of controller631 and generating an interrupt on IR03. D type flip-flop 637 is used tolengthen the pulse of device 636 to conform to the timing requirementsof controller 631.

Focusing now on FIG. 47, the two high-speed data links SERI1 and SERI2,of which SERI1 is representative, are provided by two Intel 8273 SDLCcontrollers 651 and 661. Each 8273 controller handles the low-level datalink functions and only interrupts processor 550 upon completion of aninput or output operation. The actual data transfers between SDLCcircuits 650 and 660 to ROM 601 take place through DMA cycles.

The EIA/RS232 input levels are converted to TTL levels in device 652,which is type 1489A furnished by Motorola. Moreover, output TTL levelsfrom controller 651 are converted to EIA/RS232 levels in device 653,which is type 1488 supplied by Motorola. Normally open relay 654provides contact closure K1 for controlling external Dial-Back-Up (DBU)devices over DBUA-1 and DBUB-1 leads.

Controller 651 operates in the synchronous mode wherein the externalmodem provides both the transmit and receive clock. These externalclocks appear on leads TXC-1 and RXC-1, respectively, of SERI1, and theyare converted to TTL levels by inverters 655 and 656, respectively.Controllers 651 and 661 are isolated from bus EBA with data buffer 670,which is a type 8304. Buffer 670 is enabled when either controller 651(or 661) is selected by processor 550, via CS15* (or CS9*) or during DMAtransfers via DACK12* or DACK13* leads (or DACK01* or DACK02*). Gates671 and 672 logically process these signals to enable buffer 670; itsdirection is determined by I/ORD applied to port DIR.

The final circuit of FIG. 30 remaining to be discussed, chip selector680, is shown in FIG. 48. Gates 681 and 682, each of which is type LS75,buffer external chip select leads CS4*, CS8*-CS11* and CS15* and producelocal equivalents of these chip selects. Chip selects CS10L* and CS11L*,the local signals relating to GPIB activation, are AND'ed by gate 684 toenable bus buffer 683, which is type LS245.

It should be noted here that FIG. 56 summarizes the signals appearing onbus IBE of FIG. 30.

Referring again to FIG. 28, it is seen that tier 2 interface 1421 (FIG.3), which is also representative of interfaces 1422-1468, comprisesbasically two networks, namely, the same CPU circuitry of FIG. 29 andthe I/O circuitry of FIG. 31.

With reference to FIG. 31, I/O circuitry 700 is comprised of: ROM 601',which is basically the same as ROM 601 of FIG. 30; output bus circuit620' of the GPIB T/L/C type which has basically been described abovewith reference to T/L/C 620 of FIG. 30; bus circuit 710 (GPIB23)providing a GPIB talker/listener (T/L) interface (GPIB21 and GPIB22 areessentially the same as GPIB23, so it is taken as representative);high-speed DMA circuit 720; and chip select circuit 740.

The GPIB talker/listener circuit 710 shown in FIG. 49 comprises an 8291Talker/Listener device 711 and two GPIB buffers 712 and 713 of the 8293type. Buffer 712 is arranged to operate in IEEE standard implementationMode 1 whereas buffer 713 is connected as per Mode 0. These buffers areaccessed via their respective chip selects as well as I/ORD*, I/OWR* andaddress bits A0-A2 on bus EBA. When a particular T/L circuit (GPIB23,GPIB22 or GPIB21) is selected to transfer data by master controller620', an interrupt is generated via the respective interrupt lead (IR25,IR23 or IR26).

DMA circuit 720 is depicted by arranging FIGS. 50 and 51 in side-by-sidefashion. The internal bus IBDMA at the output of the circuitry of FIG.50 serves as the input to the circuitry of FIG. 51. A 9517A DMAcontroller, shown as device 721 in FIG. 51, forms the basis of theembodiment. For high-speed DMA channels are provided, one for each ofthe four GPIB circuits. During a DMA cycle, DMA circuit 720 places a16-bit address A0-A15 on EBA. Address bits A8-A15 are latched intodevice 723, an 8282 latch, whereas bits A0-A7 are buffered by device 722of FIG. 50; this latter device is a LS245 buffer. The RD*, WR*, I/OWR*and I/ORD* signals on EBA are also asserted during a DMA cycle, and gate734, also a LS245, buffers these four signals. The AEN signal fromcontroller 721 controls the direction of devices 722 and 723, and AEN isinverted and placed on EBA to disable processor 550. A LS245, shown asdevice 725 in FIG. 51, serves to isolate bits D0-D7 on EBA fromcontroller 721 input ports DB0- DB7.

In a manner similar to the timing generation circuits of FIGS. 44 and55, that is, devices 635, 636 and 633, circuit 727 (a LS175 supplied byTexas Instruments) and gate 726 of FIGS. 50 and 51, respectively, serveto latch GPIB requests on the falling edge of the clock as well asproducing an inverted, delayed signal for DMAREQ*.

The internal EOP* signal of controller 721 is a bidirectional "end oftransfer" signal. During output transfers, when the last byte of theGPIB message has been sent, EOP* is asserted low. This assertion isinverted and produces an interrupt on IR07. During input transfers ofthe GPIB type, the "end of transfer" signal is generated, as per FIG.52, by devices 728, 729 and 730 as well as the associated OR andinverter circuits. Each device 728, 729 or 730 is a LS74 furnished byTexas Instruments. The EOI* leads associated with the various GPIBbusses, that is, EOI0*-EOI3* corresponding to the T/L/C, first T/L,second T/L and third T/L (FIG. 49), respectively, are latched intodevice 728 or 729 by each rising edge of the DREQ lead from therespective GPIB controller. When the channel that is finished is grantedits DMA cycle, EOP* is pulled low by device 730, thereby disabling theproper DMA channel and generating an interrupt on IR07. Device 730 isalso used to lengthen the pulse to conform to the timing requirements ofDMA controller 721.

FIG. 53 depicts the chip selector circuit 741, a LS373 furnished byTexas Instruments, which basically transforms external bus chip selectsto internal bus chip selects. In addition, bidirectional driver 742, ofthe LS245 type, is enabled whenever any GPIB related activity isrequested. All of the signals on internal bus IBD, including the chipselects, are shown in FIG. 56.

Referring back to FIG. 28, tier 3 circuit 14001, (FIG. 3), which isconsidered as representative of circuits 14002-14096, comprisesprimarily three networks, namely, the same CPU circuitry of FIG. 29, theinput circuitry of FIG. 32 and the output circuitry of FIG. 33.

With reference to FIG. 32, the composition of the input circuit 700' isbasically the same as structure 700 of FIG. 31 just discussed. The maindifference is that, whereas FIG. 31 included one GPIB T/L/C and threeGPIB T/L circuits, FIG. 32 includes four GPIB T/L circuits. Accordingly,FIG. 32 requires no additional discussion since the realization isstraightforwardly inplemented from the implementation of FIG. 31.

Thus, the final circuit of DCN 140 requiring discussion is that depictedas output circuitry 750 of FIG. 33; it implements eight low-speed SDLCdata links 761-768 capable of operating with either synchronous orasynchronous datasets. Auxiliary circuits, namely, programmable intervaltimer (PIT) circuit 751, data buffer 752 and chip select 753 supportdata link transmissions.

Focusing on data link circuit 761 of FIG. 54, which is representative ofthe remaining seven SDLC circuits, an 8273 SDLC controller 770 handlesthe low-level data link functions and only interrupts processor 550 uponcompletion of an input or output operation. Data transfer betweencontroller 770 and RAM 540" of tier 3 (basically the same as RAM 540 oftier 1 shown in FIG. 39) takes place through transmitter or receiverinterrupts. The EIA/RS232 input levels are converted to TTL levels bydevice 771, which is type 1489 circuit. Output TTL levels from device770 are converted to EIA/RS232 levels by device 772, a type 1488circuit. Relay 773 provides contact closures for controlling externalDial-Back-Up (DBU) device connected to the far-end of serial data busSER01. This relay is driven by output port PB1* of controller 770 and isnormally deenergized.

In the synchronous mode, circuit 770 is driven by an external modemwhich provides both the transmit and receive clock. In the asynchronousmode, no external clock is provided. An internally generated clockdrives the transmitter, and the receiver is driven with an internallygenerated clock derived from the incoming data stream by aphase-lock-loop circuit within controller 770. Selector 774, when is aLS157 furnished by Texas Instruments, determines the clock configurationfor the data link SER01. The external clock is converted to TTL levelsby device 775, also a 1489-type circuit, and passed through selector 774in the synchronous mode. In the asynchronous mode, the internal clocksare selected. Lead SYNC-1 on link SER01, when strapped to ground,selects the synchronous mode.

Each controller 770 requires three select signals, namely, one foraccessing its registers, one for transferring output data, and one foraccepting input. Address leads A0 and A1 select the registers withincontroller 770. Address leads A2, A3 and A8 control decoder 776, aSN74LS137J produced by Texas Instruments. Two controllers can besupplied by one decoder 776, via CS*, RXDACK* and TXDACK* of eachcontroller 770; one controller is shown in phantom in FIG. 54. Gate 777activates decoder 776 when one of the controller pairs requiresservicing.

Auxiliary circuit 751, a 8253 PIT, shown in FIG. 55, provides localtiming signals. Circuit 751 is accessed from EBA by asserting CS28* orI/ORD* or I/OWR*. Address leads A0 and A1 are used to select the variousinternal registers of the PIT. Three programmable outputs are available.The signal on OUT0 is used as a divide-by-two circuit to insure a 50%duty cycle for clock SDLCCLK. OUT1 is used as the 1XCLK clock source forSDLC's 761-768 when used in the asynchronous mode; OUT2 is used as the32XCLK clock source for the internal phase-locked-loop of controller770.

The eight SDLC's 761-768 are isolated from external bus EBA bybidirectional driver 752, an 8304 buffer. Driver 752 is enabled when anyof the eight SDLC's are selected. Gate 754, a NOR circuit, logicallyenables driver 752; its direction is determined by I/ORD*. Latch 755, aLS373 type, latches the eight chip selects at its input to insure driver752 stays enabled for the desired time interval.

Because of hold-time limitations on controller 770, all chip selects arelatched into latch 753, also a type LS373, with a signal generated bystretching the I/ORD* signal with interposed gate 756.

FIG. 56 summarizes the signals appearing on internal bus IBC. Thebuffered chip select signals CS9L*-CS11L*, CS17L*, CS30L* and CS31L*enable the SDLC controllers 761-767, not shown in FIG. 33, just asCS29L* and CS8L* enable controller 770 and is mirror-image counterpart.

3.1.2. DCN Programs

A listing of the programs for operating the microprocessors comprisingtiers 1, 2 and 3 of the illustrative embodiment of DCN 140 is includedas a set of appendices in Rubin Ser. No. 399,177, filed on even datedherewith as indicated in the Cross-Reference to Related ApplicationsSection. In particular, Appendices A, B and C of Rubin Ser. No. 399,177present the programs, as well as supplemental information, which willaid one skilled in the art to program and operate, respectively, eachtier 1, tier 2 and tier 3 microprocessor. These microprocessors arerepresented by the one discussed with reference to device 551 of FIG.36. The information presented by an Appendix A, B or C of Rubin Ser. No.399,177 is divided into the following parts: (1) a table of programnames in alphabetical order as per source code name; (2) the listing foreach source program; (3) routines for associating related source codeand for organizing the memory space; and (4) the memory map.

The majority of the programs are written in the C language; these arerecognized by ".c" at the end of each program name (e.g., TLCtask.c inAppendix A of Rubin Ser. No. 399,177, the GPIBTalker/Listener/Controller task program which implements PARALLEL OUTPUTtask 11407 of FIG. 7). The C language is a well-known high-levellanguage that is comprehensively described in a book entitled "The CProgramming Language" as authored by B. W. Kernighan and D. R. Ritchieand published by Prentice-Hall in 1978.

Some programs are written in the assembly language of the BELLMAC-8microprocessor. These programs may be recognized by the ".s" suffix in aprogram name (e.g., boot.s). This assembly language is patterned afterthe C language and, in fact, possesses many of its high-level languageconstructs. One skilled in the art of C programming may readily programin the BELLMAC-8 microprocessor language once it is understood thatcertain register designations in register-related instructions arelocated in RAM (as compared to on-board, hardwired registers). Inparticular, there are two register sets, one 8 bits in length and theother 16 bits. Moreover, each set comprises 16 registers and thelow-order 8-bits of a 16-bit register actually comprises one of thecorresponding 8-bit registers and, therefore, may be separatelyaddressed.

Other programs, although written in the C language, do not appear withthe ".c" suffix, but rather have a ".h" or ".H" appended to the name(e.g., gpib.h or nadmintask.H in Appendix A of Rubin Ser. No. 399,177).In the C language, these are known as "include" files and are basicallylibrary files. These programs are generally called upon by many users.If each separate user had a private copy, then each time a change wasmade, all users would have to be so advised and each user would berequired to incorporate the change to remain current. To mitigatepotential errors in such a procedure, the subject program is placed in asource library and only the library copy is altered. The numerous userscall upon the library copy during a program activity with the assurancethat the library copy is up-to-date.

The three remaining entries in the tables, namely, dcnj.mk, dcn.j.i anddcnj.out MAP, j=1, 2 or 3, have the following meanings; (1) dcnj.mk is aso-called "make" file. It indicates to the system shich prepares objectcode from source listings the source code files that are to beconcatenated to derive a particular object code file; (2) dcn.j.iindicates to the system where in memory the object code is to belocated. Memory has three main partitions--text (.text), data (.data)and block storage (.bss); (3) dcnj.out MAP presents the memory locationof the various object modules for an executable program.

In Section 2.1c, six tasks were discussed. Five of these tasks appliedto tier 1 software, and these included: SERIAL DATA; PARALLEL OUTPUT;ADMINISTRATION; BROADCAST; and DUMP MEM. With reference to the table ofprogram names for Appendix A of Rubin Ser. No. 399,177, the followingrelationships between generic task names and actual softwareimplementation for the illustrative embodiment may be identified;x25task.c implements the SERIAL DATA task; TLCtask.c corresponds toPARALLEL OUTPUT; nadmintask.c is the ADMINISTRATION task; broadcast.c isthe BROADCAST task; and DUMP MEM corresponds to dumpmem.c. Similarcorrespondences may be made for tier 2 and tier 3 tasks by referring toAppendix B and C of Rubin Ser. No. 399,177 respectively.

The actual high-level data link protocol implemented by SERIAL DATA orx25task.c is a subset of Level 2 of CCITT X.25 protocol. This protocolis described in a reference entitled "CCITT X.25 Packet SwitchingInterface", published in February, 1978 by the DATAPRO ResearchCorporation of Delran, N.J. The particular subset is designated theBX.25 and is described in AT&T Technical Reference Publication 54001entitled "Operation Systems Network Communication Protocal SpecificationBX.25", Issue 2, made available to the public in 1981.

The SERIAL DATA task in each tier 1 device 1401-1412 controls serialdata links 9201-9224 arriving at the input of DCN 140. These serial datalinks are generally operated at a high speed, typically 9.6K baud orgreater, to achieve the desired throughput. It is evident from thethree-tier nature of DCN 140 that serial data links 93001-93768emanating from tier 3 circuits 14001-14096 are decoupled from links9201-9224. Thus, the SERIAL DATA task of tier 3, although substantiallythe same as SERIAL DATA of tier 1 in terms of source code, operates at adifferent baud rate (4.8K baud or less) because of differing clock ratesbetween tier 1 and tier 3 hardware. It is clear then that DCN 140effects baud rate conversion.

It will also be appreciated by one having oridinary skill in the artthat DCN 140 may also effect protocol conversion. Although in theillustrative embodiment the BX.25 protocol is utilized on entering aswell as exiting data links, the decoupling between tiers 1 and 3 allowsfor independent protocol realizations. Thus, links 93001-93768 could beoperated asynchronously in a different environment, or some links mayimplement the SDLC protocol and the remaining ones an asynchronousprotocol. Even if both implemented a BX.25 protocol, it is possible tohave a nonreturn-to-zero (NRZ) convention on the input links and a NRZinverted (NRZI) on outgoing links. This arrangement is also consideredone of protocol conversion.

To improve the efficiency of GPIB transmissions, a technique alreadyalluded to in Section 2.1d has been devised. The GPIB interface softwareis separated into two parts, namely, software for the Talker/Listenersof tiers 2 and 3, and software for the Talker/Listener/Controller oftiers 1 and 2. For example, with reference to FIG. 57, which depictscircuitry of FIGS. 30 and 31 recast for the present dicussion, T/L/C 620(FIG. 30) is representative of a tier 1 controller, whereas circuitry710 (FIG. 31) is indicative of one of twelve listeners loading tier 1output bus 14101. The T/L/C software supervises transactions on theappropriate GPIB bus, watches for errors and determines which bustransactions should occur at any given time. Both softwareimplementations provide throttling in case of buffer depletion, checkfor errors, retransmit messages received incorrectly and provide messagetransfer timeouts.

Within the framework of the GPIB protocol, a controller (sender) andlisteners (receivers) communicate via a second-level protocol. Thediagram of FIG. 57 is utilized to explain this secondary parallel busprotocol. Messages transferred over the GPIB data lines D0-D7 comprise acheck word (CRC-8 polynomial in the illustrative embodiment) followed bythe series of data bytes comprising the actual message. After the entireaugmented message has been received by a listener or listeners, thereceiving software computes a check value and compares it to the checkword in the message. If the word and value match, apositive-acknowledgement (ACK) is transmitted to the sending side. Ifthere is no match, some data error occurred and a negativeacknowledgement (NACK) is transmitted to the sending side.

The T/L/C side transmits an ACK to the T/L side by sending a single zerobyte (0x00) to the minor address of the T/L, shown as part of device 714in FIG. 57. The minor address is computed by adding a preselected valueto the major address; in the illustrative embodiment, this value issixteen. A NACK is transmitted by sending a single nonzero byte to theminor address.

The T/L side transmits positive and negative acknowledgements via itsserial poll register, represented by device 715 in FIG. 57. One bit isassigned to each type of acknowledgement and these are depicted by bitpositions 4 and 3, respectively, in poll register 715. The controllersoftware responds to the ACK/NACK message when it polls each T/L circuit710 in the usual fashion as set forth in the GPIB protocol standard(IEEE-488).

Each Talker/Listener also maintains in its associated serial pollregister a bit (e.g., bit position 1) indicating the presence of anempty receive buffer. Each time a change is made to the serial pollregister, such as an arrival of a free receive buffer or an ACK/NACK, aservice request (SRQ) is made (as per the IEEE-488 standard). The T/L/Cmaintains a queue of empty buffers. It will not allow any T/L device totransmit messages if no buffers are available. In addition, the T/L/Cwill not transmit any messages to a T/L device that does not have areceive buffer available. If a Listener has a message to be transmitted,it sets a designated bit (e.g., bit position 0 of serial poll register715) and issues a service request.

Each controller maintains a copy of the poll registers of its associatedlisteners. The copy is updated every time a poll is taken. Another pollregister bit (bit position 2) indicates to the controller the on-linestatus of each listener. For each T/L receiver, a queue of outgoingmessages is maintained as well as a time stamp for the top message onthat queue. If the top message is not transmitted successfully withinthe timeout interval, the T/L device is queried via specialerror-recovery software. One or more outgoing messages may be discardedor rerouted, depending on the severity of the problem.

3.2.1 LTS Controller Implementation

With reference to FIG. 11 in the way of recapitulation, LTS controller2000 provides the following functions:

(1) control of communications over serial data link 930 between LTS 160and DCN 140;

(2) control of GPIB communication bus 20001 over which PMU's 2101-2103and port controller 2200 transmit data to and receive data from LTScontroller 2000;

(3) scheduling of PMU's 2101-2103 and their connection to an accessedloop 180-184;

(4) control of DDD network, via DDD circuit 2400, and the interactivetesting arrangements;

(5) transmission of test requests to PMU's 2101-2103 and port controller2200;

(6) collection of test results from these same entities; and

(7) timing of all requests.

As depicted in the leftmost portion of FIG. 58, LTS controller 2000comprises basically three networks, namely, main controller 2045, bankmemory 2050 and line interface 2070. In fact, as indicated by the blockdiagrams of FIG. 58 relating to port controller 2200 and PMU controller3100, controller 2045 of FIG. 59 and bank memory 2050 of FIG. 69, withminor variations, are implementations adaptable to these threecontrollers embedded within LTS 2000.

3.2.1a LTS Main Controller Circuitry

Now with reference to FIG. 59, the circuitry of LTS main controller 2045comprises: microprocessor devices 2001 and 2008 and associated processorcontroller 2002; GPIB interface circuitry including adapter 2020 andcontroller 2021; clock and timing circuitry including oscillatoor 2004,clock divider 2005, timer 2030 and reset 2010; memories 2042 and 2043 aswell as chip select decoder 2015; interrupt circuitry 2025; and numerousdata, address and control buffers 2003, 2007, 2022, 2023, 2040 and 2041.Each of the networks depicted by the block diagram of FIG. 59 is nowdiscussed in more detail.

Referring now to FIG. 60, device 2001, in the preferred embodiment, isalso a BELLMAC-8 microprocessor and its associated process controller2002 is a type 129CY timing generator. Internal address leads A00-A15 ofdevice 2001 are transformed into external bus address leads LAB00-LAB15via buffer 2003 (BUF3), although address leads A00 and A01 are latchedinto controller 2002 before connection to buffer 2003. A pair of S244line drivers cooperate to form buffer 2003. The buffered address leadsLAB00-LAB15 serve as inputs to other circuits of FIG. 59 as well asappearing on the external bus EBL.

Internal data leads D0-D7 originating on device 2001 connect to buffer2040 (BUF4) of FIG. 61 via internal bus IBL. Buffer 2040 is a type 8304transceiver and the direction of propagation of logic signals throughbuffer 2040 is controlled by the READ signal designated LRD*. The databits appear on bus EBL as bits LDB00-LDB07. In addition, since data bitsLDB00-LDB07 are utilized for memory accessing information, these bitsare buffered from RAM1 2042 and RAM2 2043 of FIG. 64 by transceiver 2041(BUF6), another type 8304. Device 2041 is enabled via the CD* signal andits direction is controlled by the AND'ing of the LRD* and LRDP*signals.

The clock signal for timing device 2001 is derived from oscillator 2004and clock divider 2005 of FIG. 63. Oscillator 2004 produces asquare-wave output with a frequency of 4.0 MHz. Clock divider 2005 is aneight stage counter, but only three outputs are selected. In particular,CLKA, CLKB, and CLKC correspond, respectively, to 15.625 kHz, 2 MHz and62.5 kHz. CLKB is buffered and transmitted over IBL to drive device 2001at its resonator input (CLKIN); inverter 2006 connected between CLKB andCLKIN raises the clock signal level to that required by device 2001.

Microprocessor 2001 has its reset input (RESET*) connected to the RC*output of controller 2002. Thus, a reset is generated whenever alow-going signal is applied to the RR* of NMIR* ports of controller2002. As depicted in FIG. 62, the RR* signal is basically a bufferedversion of the master reset input (LIMRST*). The master reset output(LOMRST*) is developed from NOR'ing the RR signal and the software resetsignal; the latter is generated whenever a write operation is performedto a particular memory location, which is chosen as 0xF800 in theillustrative embodiment.

Controller 2002 generates write and read signals LWRP* and LRDP* ,respectively, for use with standard peripheral devices. These signalsare buffered via line driver 2007 (BUF5) or FIG. 60; driver 2007 is alsoa S244 device. Controller 2002 causes the DATA READY (RDY) lead ofdevice 2001 to go low for one clock cycle whenever the WSS* ofcontroller 2002 is brought low. The insertion of a wait state (WSS*) isrequired in order to generate the LWRP* and LRDP* signals.

The control of direct memory access is provided by flip-flop device 2008and NAND gate 2009 of FIG. 60. This arrangement produces a delayedLDMAACK* signal whenever a LDMAREQ* is asserted. Additionally, the DMAcircuitry causes the insertion of a wait state into the cycle time ofdevice 2001 following the end of a DMA operation. This occurs whenever aLDMAREQ* is asserted and device 2008 provides the delayed LDMAACK* sincebuffers 2003, 2007 and 2040 are placed into the tri-state conditionuntil the end of the DMA access cycle when LDMAACK* goes high.

Decoder 2015 of FIG. 59 is comprised of PROM 2016 and latching 3-8decoder 2017 shown in FIG. 63. PROM 2016 is Texas Instrument type 28L22programmed so that all addresses A0-A7 in the range 0x00 to 0xF5 havedata bits that are all 1's, whereas addresses 0xF6-0xFF have thefollowing hexidecimal data, respectively; CF, CF, EE, ED, EB, E7, BF,BF, BF and 6F. Outputs K0-K3 are the chip select signals for RAM1 2042of FIG. 64. The IOE* output is converted to the system input/outputenable LIOE* via buffer 2007 of FIG. 60. The K4* output is thechip-enable signal for RAM2 2043. The K4* signal is AND'ed with thesignal appearing on Q4 of PROM 2016 to provide the CD* signal whichenables buffer 2041 of FIG. 64. Finally, output Q7 of PROM 2016 is thedecoder enable signal for decoder 2017. The Q7 output also forces WSS*of controller 2002 low to cause the generation of a peripheral accesscycle via LSWAIT* .

Decoder 2017, typically a LS137, provides local decoding information.For instance, K9* is utilized for software reset (FIG. 62) and to enableGPIB adapter 2020 of FIG. 61. The DBIN signal, which is an inverted,buffered version of LRDP* (FIG. 61), is used to latch the outputs ofdecoder 2017 to avoid changing chip selects until LRDP* has becomeinvalid.

The GPIB interface circuitry comprises adapter 2020 of FIG. 61,controller 2021, data bus transceiver 2022 (BUF1) and controltransceiver 2023 (BUF2), the latter three elements being depicted inFIG. 62. Adapter 2020 serves as the GPIB address register and is type81LS95 supplied by National Semiconductor. The GPIB0-GPIB2 status leadson bus EBL correspond to inputs A8-A6, respectively. Adapter 2020 isselected by a read from a specific memory location, in this case 0xF800,which generates the K9* signal. As suggested above when FIG. 58 wasdiscussed, the circuitry of FIG. 59 serves as a foundational element forLTS (2000), port (2200) and PMU (3100) controllers. Selection of theproper configuration in the specific environment is effected by thestatus of leads GPIB0-GPIB2. For instance, if the circuitry of FIG. 59is to serve as LTS main controller 2045, the GPIB0-GPIB2 leads aregrounded. In terms of a bit pattern, the status may be summarized as`000`. If the circuitry serves as port main controller 2245, a `001` bitpattern describes the state of leads GPIB0-GPIB2 with GPIB2 being thehigh or `1` bit.

Controller 2021, which is a 9914 supplied by Texas Instruments, can beprogrammed to operate as a Talker, a Listener or Controller or anycombination of each depending on the environment. For the LTS, it is aT/L/C. Chip enable is supplied by K12* and register select lines RS0-RS2by leads LAB00-LAB02 from bus EBL. Transceiver 2022, a SN75160 devicefurnished by Texas Instruments, buffers controller 2021 from bitsLI01-LI08 on the GPIBL bus. Similarly, transceiver 2023, a SN75161device also furnished by Texas Instruments, buffers the conventionalGPIB control leads appearing on bus GPIBL to controller 2021.

Interrupt control section, depicted by block 2025 in FIG. 59, comprisesinterrupt controller 2025 (a PIC 9519) and D-type flip-flop 2027 (a LS74type device) both shown in FIG. 61. Controller 2026 is selected by K13*and enabled by address lead LAB00. The interrupt requests appear onleads LIR01*-LIR06* emanating from bus EBL. Internal interrupt requestlines IREQ2 and IREQ7 are serviced by GPIB controller 2021, via theINTGPIB* lead, and timer 2030 via its OUT2 port. Device 2027 is the PICenable circuit which insures that the PAUSE output is disabled until asoftware initialization has occurred. This flip-flop is reset any time aCPUR* feeds its CLR input; CPUR* is generated whenever processcontroller 2002 outputs a reset (RC*). To enable PAUSE, an access oflocation 0xFE00 must be performed. When controller 2026 receives anyinterrupt request at any of its interrupt ports, it generates a GINT*signal. This signal serves to interrupt device 2001 and thereby causesdevice 2001 to perform an interrupt vector read of location 0xFFFF. TheLIACK* signal is generated by device 2001 when a read operation isperformed on any locations from 0xFF00 to 0xFFFF. A low LIACK* with avalid LIR01*-LIR06* causes the PIC to place an eight-bit interruptvector onto its DB0-DB7 ports. During this sequence, PAUSE will go lowto allow the PIC to determine the priority and vector corresponding tothe associated LIR01*-LIR06* input. There is also a nonmaskableinterrupt facility provided by controller 2002 and gate 2011 of FIG. 60.If LNMIR* is brought low, then the NMIF port of controller 2002 goeshigh and an RC* signal is generated. The NMIF output can be read byaccessing location 0xFA00 where bit 7 contains the NMIF state.

Interval timer 2030 of FIG. 59 is PIT device 8253 of FIG. 61. This timeris selected by K14* and address leads LAB00 and LAB01. The PIT containsthree independent sixteen bit counters with CLK0, CLK1 and CLK2 servingas the input ports to these counters. CLKA, CLKB and CLKC provide theinput drive to these clock ports. The output of the first counter, onOUT0, provides nonbuffered clock output LAUXCLK. The output of thesecond counter, on OUT1, is buffered by device 2007 and appears on busEBL as LCKLOUT. The third counter output, OUT2, generates an interruptpulse every 100 msec. to provide timing for the software operatingsystem.

The memory section of FIG. 64 depicted by RAM1 2042 comprises four 2K×8RAM devices 61A, which are selected (E*) by K0-K3, respectively, arewritten with LWR*, read by LRD* and addressed by LAB00-LAB10. Anadditional 4K of RAM is provided by RAM2 2043 comprising eight 4K×1static devices 39A furnished by the Western Electric Co. Each output bitfrom the eight devices comprising RAM2 is grouped with the other outputbits to form data bits MD0-MD7. The combination of RAM1 and RAM2provides 12K bytes of RAM which is memory-mapped in the range0xB000-0xDFFF. A more detailed memory map will be discussed shortly.

A summary of the signals appearing on both external bus EBL and internalbus IBL is presented by line diagrams of FIG. 65.

3.2.1b LTS Universal Memory

Universal memory 2050, shown in block diagram form in FIG. 69, is usedfor three different applications in LTS 160 (FIG. 11); it provesexpedient to discuss them at this point and later discussion need onlymention them in passing. Memory 2050 supplies LTS controller 2000, portcontroller 2200 or PMU controller 3100 (FIG. 17) with 64K bytes of ROM.This memory is divided into banks that are dynamically mapped into theaddress space of an individual controller as needed. For instance, FIG.66 depicts 64K of addressable memory space (0x0000-0xFFFF) in theordinate direction. The 20K of memory from 0xB000-0xFFFF, combining BANKA2 with BANK A3, is provided by LTS main controller 2045 of FIG. 59, asdiscussed above. Of this 20K, BANK A3 is allocated to I/O functions.

The memory from 0x0000-0x4FFF, shown as BANK A, represents 20K of ROMprovided by universal memory 2050. This bank is never switched. However,the memory space 0x5000-0x9FFF, at any given time, may be provided byBANK B, BACK C or the combination of BANK D and BANK D1. The formerthree banks are located on universal memory 2050 and are switchedaccording to the particular task requiring processing. BANK B and BANK Care both 20K, but BANK D is only 4K. Thus, whenever BANK D is switched,a simultaneous switch is made to BANK D1, which is 16K of ROM located ondata line interface circuitry 2070 of FIG. 72 (to be discussed shortly).The final 4K of memory, from 0xA000-0xAFFF, is RAM provided by interfacecircuitry 2070 of FIG. 72. FIGS. 67 and 68 show memory allocation andprovisioning for port controller 2200 and PMU 2101, respectively, andthese allocations will be discussed later.

Now with reference to FIG. 69, universal memory 2050 is composed of datatransceiver 2051, address buffer/decoders 2052-2056, memory bankselector 2057 and ROM memory section 2060.

As depicted in FIG. 70, data transceiver 2051, a 8304 type device,provides buffering and bidirectional drive for the system data lines []DB00-[ ]DB07. (The brackets [ ] indicate that the controllerdesignation is inserted where applicable; thus, for LTS controller 2000,L is substituted for [ ]; a P applies to port controller 2200; and Rapplies to PMU controller 3100). The direction of propagation isdetermined by the system read lead [ ]RD* appearing on external bus EBM.

For each application of memory 2050, a unique decoding format iscontained in the three PROM's 2054-2056; these PROM's are type 28L22 inthe preferred embodiment. In particular, for LTS operation (Lsubstitutes for [ ]), one particular chip select in the rangeMCS0*-MCS4* is activated for BANK A operation, a chip select MCS5*-MCS9*for BANK B, a chip select MCS10*-MCS14* for BANK C, and chip selectMCS15* for BANK D.

There are two types of operations that involve accessing memory 2050.These operations are "memory read" and "bank selct". Both operationsbegin by placing an address on memory address leads [ ]AB00-[ ]AB15. Theaddress bits on these leads are buffered by line drivers 2052 and 2053,which are S244 type devices. If a memory read is required, the addressmay range from 0x0000 to 0xFFFF. On the other hand, if a bank select isdesired, the address supplied is 0x0000. Address leads [ ]AB00-[ ]AB11are presented, via lines MAB0-MAB11, directly to memory section 2060 ofFIG. 71. This section 2060 comprises sixteen 4K×8 ROM devices of thetype 2732A supplied by Intel. Four such ROM devices are depicted in FIG.71. ROM 2061 is enabled by chip select MCS0* so it forms a portion ofBANK A. ROM 2062 is a portion of BANK B and it is enabled by MCS7*. Thesixteenth device, ROM 2064, is assigned to BANK D and it is enabled byMCS15*.

The remaining address lines MAB12-MAB15, as well as MAB11, are presentedto decoder devices 2054-2056. Devices 2054 and 2055 generate theone-in-sixteen chip selects whereas device 2056 generates the enable fortransceiver 2051. When a bank select operation is desired, the [ ]WR*signal is pulled low. This forces transceiver 2051 into the write modeand upon the rising edge of the write pulse, the lower four bits of databus [ ]DB00-[ ]DB07 are latched by selector 2057, a 74LS379 supplied byTexas Instruments. Bits MDB0 and MDB1 are presented to decoders2054-2056 for selction of the appropriate BANK (B, C or D) to beassociated with BANK A. In addition, MDB2 and MDB3 are buffered byselector 2057 and appear on bus EB[ ] as [ ]MB and [ ]MBD, respectively;these two signals enable memory within LTS main controller 2045 and dataline interface 2070.

If a memory read operation is desired, the read line [ ]RD* is pulledlow, thereby enabling memory section 2060 to output data bits MDB0-MDB7and forcing transceiver 2051 into the read mode. Thus, the contents ofthe addressed memory location are available on [ ]DB00-[ ]DB07.

3.2.1c LTS Serial Data Line Interface

Data line interface circuitry 2070, shown in block diagram form in FIG.72, provides the primary functions of (1) interfacing full-duplex serialcommunication link 930 connecting DCN 140 and LTS controller 2000, (2)furnishing 4K of RAM required by BANK A1 (FIG. 66) and 16K of ROM forBANK D1, and (3) generating numerous enable signals for talk circuits2301-2306, direct distance dialer 2400, ringing distributor 2500 andaccess network 2700. As depicted in FIG. 11, these enable signals aredelivered to the various circuits via bus 20002.

Referring now to FIG. 73, decoding for interface circuitry 2070 isprovided by device 2071, a 28L22 bipolar PROM. Decoded outputs appear onports D01-D08 of device 2071, which is coded as follows: all memorylocations contain 0xFF except locations 0x6C-0x6F, which containhexidecimal EE, EE, ED and ED, respectively; 0x70-0x75 contain hex EB,EB, E7, E7, DF, DF; 0x7C and 0x7D, as well as 0xFC and 0xFD, contain hexBF and 7F, respectively, and, finally, 0xF4 and 0xF5 both contain 0xDF.

ROM devices 2072-2075, which are 4K×8 EPROM's, provide the 16K bytes ofmemory designated BANK D1 in FIG. 66; in the preferred embodiment, thesedevices are type 2732A. Decoder outputs D01-D04 are the correspondingchip select signals, and system line LRD* furnishes the read signal.Bits DB0-DB7 combine to form the desired output byte. This data byte isbuffered from the system data bus bits LDB00-LDB07 by transceiver 2084of FIG. 75, which is a type 8304 device.

RAM devices 2076-2083, which are 4Kx1 fully static RAM's, provide the 4Kbytes of memory designated BANK A1 of FIG. 66; in the preferredembodiment, these devices are type 39A. Decoder output D06 provides theappropriate chip select and line LWR* enables a write operation. Eachone-bit input or ouput from these devices is grouped to form internaldata bus bits DB0-DB7.

The SDLC circuit comprises devices 2085-2089 of FIGS. 74 and 75 as wellas clock select circuit 2090-2091 of FIG. 74. In FIG. 74, controller2085 is an Intel 8273 type device. Controller 2085 is addressed by theK1* signal. Latching device 2089 of FIG. 75, a LS137, is a latchingdecoder used to generate K1* as well as RXDACK* and TXDACK* controlsignals. Device 2088 of FIG. 75, a LS75, latches address inputs A2-A4and chip-enable INTFE*. The LRDP* signal is used to latch the outputs ofdecoders 2088 and 2089 thereby eliminating address changes during avalid LRDP*. Buffer devices 2086 and 2087 of FIG. 74 perform RS232-TTLand TTL-RS232 level conversions, respectively. In the preferredembodiment, these devices are types 1489 and 1488, respectively.

Device 2090 and gate network 2091 form the baud clock select circuit. Ifsynchronous data set operation is desired, SYNCE is grounded and clocksTC and RC from the data set (not shown) are converted by circuits 2090and 2091 to corresponding clock inputs TXC* and RXC* for controller2085. Transmit and receive interrupt requests for data communication arefurnished by LIR01* and LIRO2*, respectively, appearing on external busEBL.

Reset circuit 2092 of FIG. 75 provides the system master reset signalLIMRST*. When both positive supplies reach their respective potentials,monostable 2093 triggers, thereby generating LIMRST*.

Not explicitly shown in data line interface circuit 2070 of FIG. 72 arethe decode circuits providing enables signals for talk circuits2301-2306, DDD circuit 2400, ringing distributor 2500 and access network2700 of FIG. 11. Basically, address leads LAB06-LAB10 provideone-in-twenty individual decode signals which function as chip selectsfor twenty ancillary control registers. Each talk circuit, the DDDcircuit, the ringing distributor or access network 2700 is controlled byappropriate chip selects. (General operation of the switching matrixwill be discussed shortly). The twenty decode signals comprise bus 22001of FIG. 11.

3.2.1d LTS Programs

A listing of the programs for operating the microprocessor within theillustrative embodiment of LTS controller 2000 is included as Appendix Dof Rubin Ser. No. 399,177. This microprocessor is the one represented bydevice 2001 of FIG. 60. The same format employed in the presentation ofprogram information for DCN 140, that is, Appendices A, B and C of RubinSer. No. 399,177, is utilized therein for Appendix D also. Thus, thetable of contents, the listings themselves, the utility routines and thememory map may be gleaned from the material of that Appendix D.

3.2.1e Tests Sequences

As summarized in Section 2.2.1c, system test requests are controlled byLTS 160 although they are actually performed by PMU 2101, 2102 or 2103.The test circuit configuration established by LTS 160 as a result ofthese requests is discussed in detail in the following material. Item(i) in each case is the test definition whereas item (ii) presents themeasurements performed.

1. AC3TY--AC Thevenin Admittance Test

(i) This test applies an AC voltage and measures the real and imagingaryparts of the TIP-to-GROUND (T-G), RING-to-GROUND (R-G) and TIP-to-RING(T-R) current flow. Using these measurements, application programs in FEcomputer 220 or 221 evaluate the real and imaginary parts of the threeterminal AC admittance. FE computer 220 or 221 specifies in the testrequest the AC voltage and frequency to be used during the measurements.Usually, these parameters are 10 V AC rms and 24 Hz (5 V AC rms for keytelephones).

(ii) In test A, the requested AC voltage is applied to both TIP and RINGand the real and imaginary parts of T-G and R-G currents are measured.

In test B, the requested voltage, at the same frequency of test A, isapplied to the RING while the TIP is grounded. The real and imaginaryparts of the T-G current are measured. (If this test is run at the sametime as the DCT, to be discussed below, the voltage is applied to thesame conductor as required in test C of DCT).

A final step in this sequence is to short TIP and RING to GROUND through8K ohms for a period of 100 msecs, in order to discharge the line so asnot to interfere with subsequent tests.

The following test results are returned;

Test A:

`icosA₋₋ TG`--real part of T-G rms current;

`isinA₋₋ TG`--imaginary part of T-G rms current;

`icosA₋₋ RG`--real part of R-G rms current

`isinA₋₋ RG`--imaginary part of R-G rms current;

Test B:

`icosB`--real part of T-R rms current;

`isinB`--imaginary part of T-R rms current;

Parameters;

VAC--voltage applied in tests A and B;

FREQUENCY--frequency used in tests A and B.

2. ACDC₋₋ I--Short-circuit DC and AC Longitudinal Current

Short-circuit DC and AC rms (0-3 kHz) currents are measured T-G and R-G.If saturation occurs because the peak of T-G or R-G current exceeds 125ma, a 4:1 current division network is inserted and the test is repeated.

(ii) The longitudinal DC and AC rms currents with the near-end shortedto GROUND are measured in the TIP and RING, with or without the currentdivision, as required. Corrections for current division are made in theappropriate PMU, and the following data are returned: `DC-TG`, `DC-RG`,AC-TG`, `AC-RG`.

3. BAL--Longitudinal Balance

(i) A longitudinal voltage betwen 0 Hz and 2550 Hz is applied to bothTIP and RING, and the resulting metallic voltage is measured. The usualfrequency is 200 Hz.

(ii) A voltage V_(AC) =50 V AC rms is applied longitudinally as depictedin FIG. 76 and the resulting metallic (I_(T) -I_(R)) and RING (I_(R))rms conductor currents are measured. The following data are returned:(I_(T) -I_(R))² and I_(R) ².

In FE computer 220 or 221 the positive square root of the current datais taken and the loop balance is obtained as follows:

if (I_(R) ≦10.5 ma), K=900-800000 I_(R) /V_(AC) ;

if (I_(R) >10.5 ma), K=1300-2712000 I_(R) /V_(AC) ;

BAL=20 log₁₀ (V_(AC) (K|I_(T) -I_(R) |)) dB.

4. DCT--Regular DC Thevenin Test

(i) This test measures the DC and AC longitudinal short-circuit currentsin the TIP and RING conductors, as well as the currents that flow whenspecified DC voltages are applied T-G, R-G and T-R. The requesting FEcomputer determines the DC resistance T-G, R-G and T-R, and alsodetermines the values of any DC sources attached to the loop under test.

(ii) In test A, the same measurements as in ACDC₋₋ I are made. If the ACresults of this test exceed a threshold of 12.5 ma rms, no further testsare performed because the loop is considered too noisy.

In test B, a DC voltage is applied both T-G and R-G and the TIP and RINGDC currents are measured. The DC voltage applied is +70.4 V if the DCshort circuit currents of test A are less than or equal 2 ma. If the 2ma threshold is exceeded, the voltage applied is ±35 V DC. The polarityof this voltage is chosen to oppose the larger of the two DC currentsmeasured in test A. If the DC current results in saturation (exceeds 125ma DC), test B is repeated at successively lower voltages of 35 V and12.6 V DC. If the current still exceeds 125 ma, DCT testing ends and theTHEV test, which will be discussed shortly, is run. The THEV test is thedefault test whenever DCT results in saturation.

In test C, the same voltage arrived at in test B is applied to eitherTIP or RING, depending on which conductor had the larger short circuitDC current flow in test A; the other conductor is shorted to GROUND. TheDC currents in TIP and RING are measured. If saturation occurs, thevoltage is again successively reduced.

The final step in this sequence is to short TIP and RING to GROUNDthrough an 8K ohm resistor for about 100 msec.

The information returned to the FE computer is as follows, depending onthe test status:

TST₋₋ NOISY--only the short circuit DC and AC rms noise currents appearin the test results.

TST₋₋ SAT--no results are returned to the FE computer and the completeresults of the THEV test replace the DCT tests.

TST₋₋ FL--measuring equipment failure so no data returned.

TST₋₋ OK or TST₋₋ DSPTO--the complete set of test results as follows:

`iDC₋₋ TG`--TIP conductor longitudinal short circuit DC current of testA;

`iDC₋₋ RG`--RING conductor longitudinal short circuit DC current of testA;

`iNSQ₋₋ TG`--TIP conductor longitudinal short circuit noise current oftest A in rms-squared;

`iNSQ₋₋ RG`--RING conductor longitudinal short circuit noise current oftest A in rms-squared;

`ioB₋₋ TG`--TIP conductor longitudinal current of test B;

`ioB₋₋ RG`--RING conductor longitudinal current of test B;

`ioC₋₋ TG`--TIP conductor longitudinal current of test C;

`ioC₋₋ RG`--RING conductor longitudinal current of test C;

`VDCA`--the magnitude and polarity of the DC source applied to the TIPand RING in test A (for DCT, this is always zero);

`VDCB`--the magnitude and polarity of the DC source applied to both TIPand RING of test B;

`VDCC₋₋ TG`--magnitude and sign of the DC source applied T-G in test C;

`VDCC₋₋ RG`--magnitude and sign of the DC source applied R-G in test C;

A TST₋₋ DSPTO (DSP Time-out) status indicates that the measurement didnot settle before a PMU time-out occurred and that the accuracy of thedata is questionable.

5. DC3TY--Thevenin Tests for DC and AC Simultaneously

(i) This test combines AC3TY and DCT described separately above.

(ii) In test A, test A of DCT is performed.

In test B, test A of AC3TY and test B of DCT are performed sequentially.

In test C, test B of AC3TY and test C of DCT are performed sequentially.

The final step is to dissipate stored energy.

6. DTA--Dial Tone Analysis

(i) This test determines whether dial tone can be drawn, whether dialtone is slow, and whether dial tone can be broken. The FE computerrequesting the test indicates the test configuration to be used, thatis, which loop conductor is to be grounded in order to draw dial tone orwhether TIP and RING should be joined together.

(ii) In test A, the metallic noise current I_(T) -I_(R) of FIG. 77 ismeasured as follows:

LOOP START: relay contacts as in FIG. 77;

RING GROUND START: close relay contact K2;

TIP GROUND START; close relay contact K1.

If the noise level exceeds a pre-set threshold, no further tests areperformed.

In test B, dial tone is drawn by operating relay K3 and closing K3contacts to connect the 20.5 ma current source as follows:

LOOP START: close relay contacts of K3;

RING GROUND START: K3 and K2 contacts closed;

TIP GROUND START: K3 and K1 contacts closed.

The length of time it takes to draw dial tone and the level of dial tonerelative to the noise level measured in test A is determined bymeasuring I_(T) -I_(R) and comparing this result with predetermined timeand level thresholds. If dial tone cannot be drawn, test C is notexecuted. Dial tone must be continuous for at least one second to be avalid dial tone. If it is present for less than one second, it isinterpreted as a one second burst.

In test C, after dial tone has been drawn for more than one second,relay K3 is relesed and the breaking of dial tone is measured.

One of the following test results is returned to the FE computer:

CAN DRAW, CAN BREAK

CAN DRAW, CANNOT BREAK

SLOW TONE, CAN BREAK

SLOW TONE, CANNOT BREAK

CANNOT DRAW

TOO MUCH NOISE

DENIAL DETECTED

7. FREQ₋₋ DETECT--Generalized Test for a Single Frequency Tone

(i) This test is performed to determine the presence of a tone whosefrequency is specified via an input parameter. One use of this test isto determine the presence of the 480 Hz tone that is used to identifylines on intercept in ESS offices.

(ii) Using the measurement circuit of FIG. 78, the rms-squared of I_(T)-I_(R) in an 8 Hz band around the specified frequency is measured.

8. THEV--DC Thevenin for Low Resistance

(i) Develop a Thevenin circuit for a circuit with low DC resistance.

(ii) After the line is discharged, in test A the T-G and R-G currentthrough 100K ohm resistors are measured and corresponding T-G and R-Gvoltages are computed.

In test B, a DC voltage is applied to TIP and RING through 8K ohmresistors; the voltage applied depends on the voltages measured in testA as follows:

    ______________________________________                                        Test A               Test B                                                   Test A Minimum Voltage (DC)                                                                        Voltage (DC)                                             ______________________________________                                        less than -60        -35                                                      -60 to -35           -121                                                     -35 to -15           -83.05                                                   greater than -15     -52.8                                                    ______________________________________                                    

The T-G and R-G currents are measured and returned to the FE computer.

In test C, the voltage value of test B is applied to the conductorhaving the largest negative voltage in test A through 8K ohm and theother conductor is connected to ground through 8K ohms. The T-G and R-Gcurrents are returned to the FE computer and then the line isdischarged.

9. OCFEMF--Open Circuit Foreign EMF

(i) Open circuit DC and AC rms currents are measured T-G and R-G.

(ii) A 100K resistor is connected between TIP and GROUND as well as RINGand GROUND. Longitudinal DC currents are measured simultaneously on TIPand RING and then AC rms current is measured on the TIP followed by aRING measurement. The following data is returned: `DC₋₋ TG`, `DC₋₋ RG`,`ACSQ₋₋ TG` and `ACSQ₋₋ RG`, where the latter two measurements occurwith a 0 to 3200 Hz bandwidth.

10. PBX3TY--PBX Thevenin Tests for AC and DC simultaneously

(i) This test is identical to DC3TY except for restrictions on appliedDC voltages so as not to alert the PBX attendant.

(ii) In test A, the longitudinal DC and AC rms (0-3.2 kHz) currents withthe near-end TIP and RING shorted to GROUND are measured, without orwith 4:1 current division, as required. If the AC results of this testexceed a threshold of 12.5 ma rms, no further tests are performedbecause the loop is considered too noisy for meaningful results.

In test B, a specified AC voltage is applied to both T-G and R-G and thereal and imaginary parts of T-G and R-G are measured. Then a DC voltageof -40 V is applied both T-G and R-G and the TIP and RING DC currents aemeasured. If the results of these DC measurements exceed a fixedthreshold, no further tests are run because the PBX trunk is too noisy.

In test C, the specified AC voltage is applied, at the given frequency,to the RING while the TIP is grounded. The real and imaginary parts ofthe T-G current are measured. Then -40 V DC is applied to either the TIPor RING, depending on which conductor had the larger short circuitcurrent flow in test A, the other conductor is shorted to GROUND. The DCcurrents in TIP and RING are measured. If saturation occurs, no furthertesting is run.

A final step is to remove energy stored in the line.

11. PBXDCT--DC Thevenin Test for PBX Equipment

(i) This test is similar to the DCT test except for restrictions onapplied voltages to prevent alerting the PBX attendant.

(ii) In test A, the AC rms short circuit currents with -40 V DC appliedT-G and R-G are measured in TIP and RING. If the results exceed a fixedthreshold, no further tests are run due to noisy trunk conditions.

In test B, -59.95 V DC is applied T-G and R-G and TIP and RING currentsare measured. If more than 125 ma flows, saturation occurs, and nofurther measurements of PBXDCT are run. The default test THEV is thenrun and the results for only the THEV test are returned.

In test C, TIP and RING DC currents are measured with -20 V DC appliedto the TIP and RING shorted to GROUND. If more than 125 ma flows, thePBXDCT test ends, and only THEV is run.

The final step is to dissipate stored energy on TIP and RING.

12. RCNT--Ringer Count

(i) This test determines the number of ringers T-G, R-G and T-R bymeasuring the magnitude of the current T-G, R-G and T-R when a voltageof 3.75 V AC rms at 5 Hz, 200 Hz, and in some cases of long loops, 85 Hzis applied to the loop.

(ii) In test A, an AC voltage is applied T-G and the magnitude of thecurrent in the R-G path is measured for each of the three frequencies--5Hz, 85 Hz and 200 Hz. If the magnitude of the 200 Hz current measurementis below a threshold, only 5 Hz and 200 Hz data are returned; otherwise,5 Hz and 85 Hz data are returned.

In test B, the AC voltage is applied both T-G and R-G and the magnitudesof the R-G and T-G currents are measured at 5 Hz and at either 85 Hz or200 Hz depending upon the evaluation of results of test A.

The following data are returned to the requesting FE computer:

`i5₋₋ TR`--peak T-R current at 5 Hz;

`iA₋₋ TR`--rms-squared T-R current at 85 Hz or 200 Hz;

`i5₋₋ TG`--peak T-G current at 5 Hz;

`i5₋₋ RG`--peak R-G current at 5 Hz;

`iB₋₋ TG`--rms-squared T-R current at 85 or 200 Hz;

`iB₋₋ RG`--rms-square R-G current at 85 or 200 Hz;

`FREQUENCY`--frequency not discarded after test A and used for test B(85 or 200 Hz).

The FE computer evaluates the ringer count from these data to estimatethe number of ringers.

13. RDA--Rotary Dial Analysis

(i) This is an interactive test requiring the interactive mode to beenabled. The customer is instructed to dial a zero after hearing a dialtone burst generated by the PMU. Pulse count, dial speed and percentbreak are measured during the return of the dial to the rest position.

(ii) The metallic current I_(T) -I_(R) is measured as shown in FIG. 79until ten pulses have been counted, but not for longer than 2 seconds.LTS 160 or 161 processes the information and returns the following, aswill be discussed in the section relating to signal processing: dialspeed in pulses per second; percent break; and one of the followingstatus messages. The messages include: Dial Speed and Percent Break OK;Good Speed, Bad Percent Break; Bad Speed, Good Percent Break; Bad Speed,Bad Percent Break; wrong pulse count; cannot measure because loopresistance too high or dial speed too slow.

14. ROH₋₋ RLS₋₋ TNK--Release of Permanent Signal Holding Trunk in SXSOffices

(i) This test is run prior to the receiver-off-hook (ROH) test on linesthat are busy without speech in order to release the permanent signalholding trunk in SXS offices.

(ii) A -40 V DC source is applied both T-G and R-G through 450 ohmresistors. The T-G and R-G currents are measured and compared with afixed threshold value to determine whether both TIP and RING have becomeopen circuits. Since the conductors may be pulsed for a time betweenopen and nonopen states, the current measurements must be timed todetermine that a true open exists. The test ends when a true open ismeasured or when an open does not occur before a preset timeout; thecorresponding status is returned to the FE computer.

15. ROH₋₋ SPUR--Spurious Energy at the ROH Measurement Frequencies

(i) This test measures offsets to be applied to the ROH test results.

(ii) The rms-squared values of the T-R current at 800 Hz and 1200 Hz aremeasured with 900 ohms connecting TIP and RING.

16. ROH₋₋ TEST--Receiver-off-hook Test

(i) This test determines if a receiver associated with customerequipment is connected across the loop.

(ii) A 400 Hz signal is applied T-R and the level of harmonic current at800 Hz and 1200 Hz is measured as per FIG. 80. From the configuration ofFIG. 90e, V_(V) is a parameter supplied by the FE computer within therange of 0.6 V to 5 V. Since V_(V) is applied with opposite phase to TIPand RING, the total rms metallic voltage is between 1.2 V and 10 V. Abias of -48 V DC may be applied to the RING when requested. Thefollowing are returned to the FE computer requesting the measurements:`i₋₋ met₋₋ 800` and `i₋₋ met₋₋ 1200` in rms-square.

The final step is to short TIP and RING to ground for about 50 msec todischarge the line.

17. ROH₋₋ VFB--Measurement of Loop Length With Possible ROH LineCondition

(i) This test determines the level of 400 Hz voltage to be appliedduring the ROH test.

(ii) A 100 Hz, 1.2 V rms signal is applied metallically through a pairof 450 ohm resistors as shown in FIG. 80, that is, V_(V) =0.6 V rms. Abias of -48 V DC may be applied to the RING when requested. The value`i₋₋ met₋₋ 100` or the rms-squared value of current is returned. Thisvalue is used to evaluate the 400 Hz tone to be applied in the ROH testso the level at the far-end of the loop is relatively independent ofloop length.

The final step is to short TIP and RING to GROUND through 8K ohms forabout 100 msec to discharge the line.

18. SOAK--Attempt to Vary Resistance of a Fault

(i) This test determines whether a resistive fault is constant, driedout or swinging as a result of applying a DC voltage.

(ii) A DC voltage specified in the request is applied both T-G and R-Gand the TIP and RING currents are measured at 0.5 second intervals for 3seconds. If a prior OCFEMF test indicates a positive foreign DC voltage,this test applies a negative voltage, and vice versa. If the magnitudeof the larger of the two DC voltages measured during OCFEMF exceeds 80 VDC, then a 40 V DC source is supplied during this test. If the voltagemeasured is less than 80 V DC, and 80.3 V DC source is supplied.

Twelve current readings are returned to the FE computer for analysis,namely, six T-G and six R-G from measurements at the end of sixintervals. The T-G and R-G resistance values are computed for all twelvecurrents; the spread in the computed resistance values determines thecharacteristics of the fault.

19. THERM--Thermistor Identification

(i) This test determines whether a thermistor is in the T-G, R-R, or T-Rpaths by applying a specified voltage and measuring the current flow. Achange of current over a prescribed interval of time indicates thepresence of a thermistor.

(ii) In test A, a 24 Hz, 32.4 V rms signal is applied longitudinally toboth TIP and RING and the current in the TIP and RING is measured after0.45 seconds have elapsed.

In test B, the currents are again measured 1 second later. If thedifference in RING current measured on test A and test B exceeds athreshold, a R-G thermistor is present. Similarly differencing andcomparing determines if a T-G thermistor is present.

If a thermistor is not detected from test A and test B, then test C isrun to test for a T-R thermistor. In this test, the T-G path is suppliedwith a series 30 V AC source, and the RING is GROUNDED. The current flowin the TIP is measured at 0.4 seconds and 2.05 seconds. If thedifference in the two currents exceeds a threshold, a T-R thermistor ispresumed to be present. YES/NO information regarding each path isreturned to the requesting FE computer.

20. SSRFAULT--Single-sided Resistive Fault Sectionalization

(i) This test is used to determine the position of a resistive faultrelative to a craftsperson at a field location. Thus, this is aninteractive test requiring the presence of personnel in the field toplace a shorting strap on the pair under test. This fault locationstrategy, as well as a double-sided fault location technique, have beendisclosed in an earlier filed U.S. patent application Ser. No. 308,417,dated Oct. 5, 1981, by J. M. Brown, and assigned to the same assignee asthe present application; the single-sided strategy is exemplary of thedisclosed subject matter.

The SSRFAULT test is utilized whenever a fault is found on only oneconductor of the pair comprising the loop under test. The craftspersonat the customer end of the loop shorts TIP and RING after disconnectingall customer equipment.

(ii) In test A, a DCT test is run initially to insure the fault liesbetween the point of testing and the point of the short.

In test B, a DC voltage V_(S) is applied both T-G and R-G. The totalcurrent on the nonfaulted conductor is measured as well as the currentdifferential between the current flow on the faulted conductor minus thecurrent flow on the nonfaulted conductor. The value of V_(S) depends onthe resistance-to-ground measurements from the DCT test. V_(S) isinitially about 70 V DC, but saturation could cause the applied voltageto be reduced to 50 V or 12.5 V DC.

In test C, a DC voltage is connected between the nonfaulted conductorand ground and the faulted conductor is grounded. The two conductorcurrents are measured. The voltage is initially 50 V DC, and saturationresults in a 12.5 V DC measurement voltage.

The four current values are returned to the requesting FE computer aswell as the voltages used in tests B and C. The loop resistance betweenthe fault and the customer end may be computed from the four currentsand the voltage of test C. The resistance is converted to distance onthe basis of the resistance per length of standard gauge telephonyconductors.

21. CN₋₋ DTF--Dial Tone First Totalizer Detection

(i) Determine the series resistance of the pair serving the coinstation.

(ii) In this test, a DC voltage is applied to the RING through 2K ohmsand the TIP is grounded. The DC applied is +30 V for DTF and -30 V forPost Pay. Both the RING current and longitudinal mode current asdetected on the TIP and measured. A longitudinal current indicates apossible relay failure in the coin station. As soon as the DC voltage isapplied, the presence of any coin tones is monitored to indicatepremature homing. The FE computer receives the two current values and aYES-NO flag depending on the results of coin tone measurement.

22. CN₋₋ TOT₋₋ DTF--Coin Totalizer Homing for Dial Tone First

(i) This test homes a totalizer that is off-home and checks itsperformance while doing so. A good totalizer will home with 18 ma orless and will return metallic tone bursts of 1537 or 1700 Hz as well as2200 Hz.

(ii) The FE computer sends six arguments to the LTS--three voltages, athreshold current and two arguments relating to options to be takenduring testing. The testing commences by applying the first voltage R-Gand measuring the RING current as well as monitoring the metalliccurrent for tone bursts. The amplitude and frequency of the coinoscillator and duration of the tone bursts are not measured precisely;the critical concern is the presence or absence of the tones. If no tonebursts are detected, the RING current is less than 17 ma and one option,called threshold, is YES, then the applied voltage is increased toprovide 18 ma within ±1 ma and the test is repeated. The second optionargument designates whether the second voltage passed between the FEcomputer and the LTS is to be used or whether the PMU is to calculatethe voltage necessary to cause 18 ma flow. All voltages, eithertransmitted or computed, rely on results of the previous CN₋₋ DTF forthe DC resistance of the loop. If no tones are detected, then the thirdvoltage (if nonzero) is applied and the RING current will be measuredwhile monitoring for tones.

If the threshold argument is NO, then the voltages as transmitted willbe repeatedly applied until tones are detected (or timeout occurs); theRING current corresponding to each applied voltage is measuredconcurrently.

Information returned from the LTS to the FE computer includes: thenumber of attempts to home before tones are detected; the voltageapplied for the final attempt; the RING current measured both at thestart and at the end of the final attempt; and the RING current at theend of the test. In addition, information relating to the frequenciesdetected and type of tone is returned as follows: BURST (1537 or 1700 or2200 Hz); NO₋₋ F; CONT₋₋ TONE (continuous tone); and BURST₋₋ TONE aswell as the number of bursts.

Tone bursts can have durations between 20 and 150 msec. Intervalsbetween bursts can be between 15 and 250 msec. If the first tone is notdetected within one second after application of a voltage, then the nextvoltage is applied. If, after the first tone is detected, no tone occurswithin 250 msec. of applying the next voltage, or a tone is continuousfor more than 250 msec., or if tone bursts continue for more than 10seconds or 38 tones, the test is terminated with a corresponding resultreturned to the requesting computer.

23. CN₋₋ CF--Coin First Totalizer Detection

(i) Determine resistance of coin totalizer.

(ii) In this test, a 26 V DC source is applied to the TIP through 2Kohms and the TIP and RING currents are measured and returned to the FEcomputer.

24. CN₋₋ TOT₋₋ CF--Coin Totalizer Homing for Coin First

(i) Home a totalizer while checking its performance.

(ii) The sequence of tests performed with this test procedure issubstantially the same as in the test above (CN₋₋ TOT₋₋ DTF). Theprimary difference is that all voltages are applied to the TIP.

25. CN₋₋ RDET--Coin Relay Circuit Detection

(i) This test is made to determine if the T-G path through the coinrelay is closed.

(ii) First, a low DC voltage (about 15 V) is applied T-G and the TIPcurrent is measured. The DC voltage is chosen so as not to operate thecoin relay circuit. If the T-G resistance is between 1800 and 3000 ohms,representing a possible "stuck coin" condition, then an AC voltage, at24 Hz, is then applied to differentiate between a stuck coin or a T-Gshort. The AC test voltage selected exceeds the DC voltage applied inthe first test. The real part of the TIP current is compared to the DCTIP current and a short is probable if the AC resistance exceeds the DCresistance. Also supplied to the FE computer is the magnitude of thesecond harmonic AC current flow to determine if the "initial rate" relaycontacts are open.

26. CN₋₋ RCR--Coin Relay Collect/Refund

(i) Determine if the collect/refund relay is operational as well asmonitoring its performance.

(ii) The FE computer supplies three voltage arguments, a thresholdargument and a current threshold, typically 41 ma. Collecting orreturning a coin is controlled by the polarity of a DC voltage appliedT-G. The DC voltage level is determined by the FE computer from resultsof the CN₋₋ RDET DC loop resistance measurement.

Three voltage arguments are supplied. The first voltage argument isapplied. If the measured current does not reach the threshold and therelay does not operate, then the PMU applies the second voltageargument. If the relay still does not operate and the third argument isnonzero, then the third voltage is applied and the timeout is set to twoseconds. Besides returning the number of attempts until the relayoperates as well as the value of the TIP current on the final attempt,the time until relay operation occurred on the last attempt is alsotransmitted. This so-called coin relay operate time is nominally lessthan 700 msec. for a nonfaulty relay.

27. CH₋₋ GRFV--Coin Ground Resistance

(i) This test determines the ground path resistance for a coin set.

(ii) The TIP, RING and ground terminals must be shorted at the coinstation. In part A, the TIP is connected to ground through 100K ohms andthe TIP current is measured. In part B, the RING is connected to groundthrough 100K ohms and the TIP is driven with 125 V DC through 1000 ohms.Both the TIP and RING currents are measured. The three currentmeasurements are returned to the FE computer where the ground resistance(R_(G)) is estimated as follows:

    R.sub.G =100K(I.sub.RB +I.sub.TA)/I.sub.TB.

3.2.2 Port Controller Implementation

With reference to FIG. 11 by way of brief review, port controller 2200provides the following primary functions:

(1) control of ports 2801-2816, sleeve lead device 2950, busy speechdetector 2600, trunk dialer 2650 and EAN 2700 to perform access totesting trunks; and

(2) control of the application of tracing tone source 2900 to a loop180-184 under test.

As depicted by the block diagram in the center of FIG. 58, portcontroller 2200 comprises basically three networks, namely, maincontroller 2245, bank memory 2250 and port interface 2270. As alreadyindicated above in Section 3.2.1 when LTS controller 2000 was discussed,port main controller 2245 and LTS main controller 2045 havesubstantially the same circuit realizations. LTS main controller 2045 isdepicted in block diagram form in FIG. 59 and is discussed in detailwith reference to FIGS. 60-65. Port controller 2245 is realized byincorporating two minor variations in the circuitry of FIG. 59. Theseinclude the reassignment of status leads GPIB0-GPIB2 of adapter 2020 andthe selection of different clock signals at the output of clock divider2005. With respect to the status leads, GPIB2 is connected to logic 1whereas GPIB0 and GPIB1 remain at logic 0 (or, in terms of a bitpattern, the status leads become `001`). Since port controller 2200 isconnected to bus 20001, this unique status lead identifier, whencombined with LTS identifier `000`, and PMU identifiers `010`, ` 011`and `100`, allows for unambiguous communication on the single GPIB bus.With regard to outputs from clock 2005, CLKC remains the same, CKLB isset for 31.25 kHz operation and CLKA is not utilized.

The memory allocation for port controller 2200 is shown in FIG. 67. The12K RAM memory space designated BANK A2 is provided by port maincontroller 2245 in the same manner this bank was provided by LTS maincontroller 2045. However, the addressable I/O space from 0xE000-0xFFFF,rather than being fully allocated to main controller 2245, ispartitioned so that 2K of the 8K is assigned to port interface 2270. Inaddition, BANK B1 and BANK C1 are mutually exclusive memory banksoccupying A000-AFFF on a switched basis; these latter 4K banks are alsoprovided by port interface 2270, as will be discussed. The threeremaining memory banks, BANK A, BANK B and BANK C, are provided byuniversal memory 2150, as now discussed.

As presented above, in the discussion of Section 3.2.1b relating touniversal memory 2050, it was stated that the universal implementationwould be adopted for port controller 2200. This is depicted in FIG. 58,wherein bank memory 2250 and port main controller 2245 are foundationalelements for port controller 2200. Bank memory 2250 is also depicted, inblock diagram form, by FIG. 69 and in detail by FIGS. 70 and 71.However, since BANK A now comprises 16K bytes and BANK B and BANK Crequire 24K bytes each (as compared to three 20K byte segments for LTScontroller 2000), PROM's 2054-2055 of FIG. 70 are programmed so thatMCS0*-MCS3* select BANK A, MSC4*-MCS9* select BANK B and MCS10*-MCS15*select BANK C. The latter two chip-select ranges are mutually exclusive,but one or the other range is always operational with the rangeassociated with BANK A.

The block diagram of FIG. 81 and the details of FIGS. 82 and 83 disclosethe primary purpose of port interface 2270, which is to provide memorycomplementing that already provided by main controller 2245 anduniversal memory 2250. The memory serving as BANK B1 in FIG. 67 isdepicted in FIG. 83 by eight 4K×1 devices 2274-2281. These static RAMdevices are type 39A. FIG. 83 also depicts the memory serving as bothBANK A1 and BANK C1 in FIG. 67; in particular, three 2K×8 devices2271-2273 provide the required 6K bytes of memory. These devices aretype 61A.

Decoding for RAM1 and RAM2 memories is provided by PROM 2283 of FIG. 82.This PROM, also a type 28L22, is coded as follows: all memory addressesare 0xFF except address 0x75, which has hex EE as data; 0x76 has 0xED;0xF5 and 0xF6 have 0xDF; and both memory ranges 0x7D-7F and 0FD-FF have,respectively, 0xEB, 0x7F and 0x7F. Address leads PAB11-PAB15 serve asinput to device 2283 as well as bank lead PMBD. A logic one on this leaddisables RAM1.

Data transceiver 2282 of FIG. 83, an 8304 device, buffers system dataleads PDB00-PDB07 from internal data leads D0-D7 which access both RAM1and RAM2.

Not explicitly shown in port interface circuit 2270 of FIG. 81 are thedecode circuits providing enable signals for ports 2801-2816, sleevelead device 2950, tracing tone source 2900, busy/speech detector 2600,trunk dialer 2650 and EAN 2700 (FIG. 11). Basically, address leadsPAB00-PAB11 provide one-in-thirty six individual decode signals whichfunction as chip selects for thirty-six ancillary control registers.These chip selects are transmitted over bus 22001 of FIG. 11.

Also not shown is circuitry realizing tracing tone source 2900. Thiscircuitry is basically conventional in that an approximately 500 Hzsource is amplitude modulated by a 1 Hz signal and when, enabled, isapplied to the loop under test.

A listing of the programs for operating the microprocessor within theillustrative embodiment of port controller 2200 is included as AppendixE of Rubin Ser. No. 399,177. Again, the format of Appendices A, B and Cof Rubin Ser. No. 399,177 is utilized to present the programinformation.

3.2.3 PMU Implementation

3.2.3a DSG Circuitry

By way of brief introduction, the MLT system utilizes AC signals tomeasure frequency sensitive loop parameters. Three separate sourcegenerators implement a synchronous, quadrature detection arrangement.One source generator supplies voltages to the loop under test, whereasthe other two source generators supply quadrature detector signals. Withreference to FIG. 18, AC source generator 3202 depicts, in general blockdiagram form, the three-generator arrangement. A more detailed blockdiagram representation of generator 3202 is shown in FIG. 84, whereinthe three generators are depicted by elements 3203, 3204 and 3205. Linegenerator 3203 supplies loop voltages, via leads 32021 and 32022, to theTIP and RING, respectively. Ring reference generator 3204 suppliesin-phase and quadrature signals for synchronous detection of the signalsappearing on the RING, where tip reference generator 3205 performs thecounterpart operation on the TIP.

In that all three generators 3203-3205 operate in basically the samemanner, ring reference generator 3204 is the only generator to bedescribed hereinafter in detail. This description proceeds with the aidof FIG. 85, which depicts the major circuit components comprisinggenerator 3204.

Ring reference source 3217 is implemented with a microcomputer; for theillustrative embodiment, this microcomputer is the Rockwell R6500/1ACtype described in detail in the following two documents: "R6500Programming Manual" published by Rockwell International In August, 1978as Document No. 29650 N30; and "R6500 Hardware Manual" published byRockwell International in August, 1978 as Document No. 29650 N31. TheR6500 is a 40-pin device comprised of: a central processing unit (CPU)that runs at half the external reference frequency of 4.194304 MHz; aROM of 2048 bytes; a RAM of 64 bytes; and various interface circuitry.This interface circuitry (not shown in FIG. 85) includes: a 16-bitprogrammable counter/latch, with four operating modes; four 8-bitinput/output ports (Port A, B, C, D of FIG. 85); five interrupt lines;and a counter input/output line. Communication with PMU controller 3100and DSP 3600 (FIG. 17), via busses 31001 and 36001, respectively, isaccomplished through Port A, a portion of Port C and two of the fiveinterrupt lines, shown as RES and NMI in FIG. 85.

Program information is transferred to generator 3204 from PMU controller3100 via Port A, that is, leads A1-A8 of source 3217. Port C (C1-C8) issplit as an input/output control port. Leads C5-C8 are manipulated byPMU controller 3100 to control source 3217. The remaining four leads areunder control of generator 3204 itself. Leads C3 and C4 inform PMUcontroller 3100 as to the operating state of generator 3204, while C2turns external counter 32171 on or off. Lead C1 is used to strobe thedigital output data appearing at Ports B and D into 8-bit MultiplyingDigital-to-Analog Converters (MDAC) 32143 and 32142, respectively. Arepresentative MDAC which may be used to implement both elements 32143and 32142 is supplied by Analog Devices. The device is numbered AD7524and is described on pages 317-321 of the "Data Acquisition ProductsCatalog" prepared by Analog Devices, Inc. in 1978.

Low-pass filters 32152 and 32153, which suppress aliasing, areimplemented in the illustrative embodiment as sixth order, Chebychev,low-pass, RC filters. Filter cutoff is set at 3230 Hz and peak-to-peakpassband ripple is 0.001 dB.

In the illustrative embodiment, microcomputer generator 3204 isprogrammed to provide a selection of output signals representing eithersingle or multiple tone test frequencies. The possible output signalsinclude:

Single Frequency--generates the AC source cosine test signal and thequadrature AC reference signals. The output is selectable in 1 Hzincrements from 1 Hz to 3200 Hz.

Burst Single Frequency--provides for timed sine/cosine pulses of achosen frequency within the 1 Hz to 3200 Hz band. The duty cycle of thepulses is programmable.

Sequence Single Frequency--generates both sine and cosine of up to 20individually programmable frequencies within the 1 Hz to 3200 Hz band.Sequencing is under direct control of PMU controller 3100.

Frequency Sweep--steps through the 1 Hz to 3200 Hz band in either theupward or downward direction. The starting frequency and upward ordownward increment is programmable. Both sine and cosine are generated,and stepping as well as choice of direction is under direct supervisionof PMU controller 3100.

Multifrequency--generates the cosine sum of any two frequency pairsbetween 1 Hz and 2000 Hz.

Sequence Multifrequency--generates a sequence of timed, multitone cosinebursts within the 1 Hz to 2000 Hz band. Capability includes thesequencing of up to 10 individual frequency pairs with the time-on andtime-off periods being programmable.

Burst Multifrequency--provides for a timed cosine pulse of a selectedfrequency pair within the 1 Hz to 2000 Hz band. The duty cycle of theburst is programmable.

In addition to these seven so-called output functions, miscellaneousfunctions to aid self-diagnostic testing are included in the programrepertoire.

3.2.3a.1 DSG Software Considerations

The software structure for Rockwell-based source 3217 (see FIG. 85) isdepicted in FIG. 86. The RESET PROCESS acknowledges the reset signal andinitializes source 3217 to a predetermined state via a signal on the RESlead. A nonmaskable interrupt (NMI) causes the NMI PROCESS to direct thetransfer of all program data from PMU controller 3100 into source 3217;the NMI PROCESS operates in response to signals on the NMI lead. Thislatter process calls on the DATA ACCEPT subroutine which is invoked toinsure the data has been properly transferred from PMU controller 3100.Moreover, the NMI PROCESS also performs the necessary "bookkeeping" inpreparation for entry into the actual signal generation subroutines. AsFIG. 86 depicts, all seven output functions defined above are dependentupon the SINCOS subroutine. It is through this subroutine that theactual samples required by each output function are selected.

The separate modules of FIG. 86, that is, the PROCESS, output functionand subroutine blocks, are now explained in depth.

(I) RESET PROCESS

As indicated above, the purpose of this process is to initializegenerator 3204 to a known state. A flowchart for this process is givenin FIG. 87. The process is entered by placing the reset lead (RES) atlogic 0 and then returning it to logic 1. This interrupt signal placesall input/output lines at a logic 1 level. It also directs microcomputer3217, via address information stored in its ROM, to the beginning of theprocess. In addition, microcomputer 3217 is set for the binary mode ofoperation, the stack pointer is set and temporary memory is loaded withzeros. Finally, both Ports B and D are loaded with a value indicative of0. volts (e.g., hex 80), and this value is strobed to converters 32142and 32143 via Port C bit 0 (C1). These converters translate the valueand produce zero volt outputs. Upon completion of the above, the processbrings C3 to logic 0. This flag indicates to PMU controller 3100 thatthe reset cycle has been completed. It also signifies that generator3204 is now waiting for data entry to indicate a request for an outputfunction.

(II) NMI PROCESS

This process has two main purposes; (1) control data transfer betweenPMU controller 3100 and generator 3204 and (2) initiate programexecution. A flowchart for this process is given in FIG. 34. The NMIlead is an edge-sensitive input line. This means that whenever ahigh-to-low transition occurs on this line, microcomputer 3217automatically sets an internal flag. This flag halts all internalprocessing and permits program execution to be vectored, via addressdata stored in ROM, to the NMI PROCESS.

Upon entering this process, microcomputer 3217 is directed to check aninternal register named FLAGS. The state of this register determinesexactly what microcomputer 3217 is to do next. There are four possiblestates for this register:

State 1: FLAGS=0 signifies that this is the first pass through theprogram so data is to be collected, via Port A (A1-A8), from PMUcontroller 3100.

State 2: FLAGS=1 indicates that all program data has been collected andthat execution of an output function is to commence.

State 3: FLAGS=2 indicates that the T-ON subroutine is to be invoked togenerate timed bursts of frequencies.

State 4: FLAGS=3 indicates that the T-OFF subroutine is to be invoked togenerate time bursts of frequencies.

Assuming, initially, that FLAGS=0, microcomputer 3217 sets the STATUSflag (C2) to logic 1. This informs PMU controller 3100 that the NMIPROCESS has been started and that microcomputer 3217 is now awaitingdata. Microcomputer 3217 now sits in a "tight" loop, polling C8 (DATAREADY). When C8 is raised to a logic 1 by PMU controller 3100, the firstprogram data byte is available at Port A.

The first data byte received is always a program identification (id)number. Upon receiving this id, a validity check is executed. Receptionof an invalid program id causes a restart (C3=0).

When a valid program id has been received, microcomputer 3217 accessesan internal table containing the starting addresses of the variousoutput functions. Another internal table is also addressed to determinea program byte count, that is, how many data bytes must be receivedbefore function execution may begin.

The byte count can be either fixed or a variable, depending upon whichoutput function is to be executed. If the byte count is fixed based uponthe program id, microcomputer 3217 signifies acceptance of the id bytethrough a "handshaking" protocol. This handshaking protocol isaccomplished with a subroutine called DATA ACCEPT (see FIG. 86); aflowchart of this subroutine is shown in FIG. 91.

A variable input byte count causes microcomputer 3217 to determine whichof two variable output functions (Sequence Single Frequency or SequenceMultifrequency) is to be executed. Acceptance of the program id byte isthen made through the handshake protocol of subroutine DATA ACCEPT. Thenext byte transmitted indicates how many more data bytes can beexpected. A check is made to insure that the expected number of databytes does not exceed a known maximum limit. If this limit is exceeded,a reset is initiated (C3=0). A valid check allows the remaining databytes to be transferred via the DATA ACCEPT subroutine.

FIG. 92 illustrates the data transfer sequence for a variable byte countrelating to the Sequence Single Frequency output function. The datatransfer indicates that this output function (id byte=hex 04) is tosequence two (M=hex 02) frequencies of 100 Hz (F-lo1=hex 40 andF-hi1=hex 06) and 200 Hz (F-lo2=hex 80 and F-hi2=hex 0C). FIG. 93indicates the bit weights to be accorded the hexidecimal data values;the use of F-lo and F-hi values will be discussed shortly. FIG. 94indicates the number and order of transmission of bytes for the variousoutput functions.

The handshaking sequence (FIG. 91) for the data transfer depicted inFIG. 36 begins with PMU controller 3100 raising C8 to a logic 1. Thissignals microcomputer 3217 of the availability of the program id databyte at Port A. Microcomputer 3217 indicates acceptance of this byte bysetting C4 to logic 1. PMU controller 3100 responds to this by placingC8 at logic 0, whereupon microcomputer 3217 responds by making C4 alogic 0. The handshake for the first data byte is now completed. Eachremaining data byte is then transferred in a similar manner.

When all data transfers have been completed, microcomputer 3217 sets theFLAGS register to State 2 (FLAGS=1) and is instructed to jump back intoa wait loop located within the RESET PROCESS. Upon entering thisprocess, the STATUS flag is reset by placing a logic 0 on C3. Thisindicates to PMU controller 3100 that the first pass through the NMIPROCESS has been completed.

Upon receiving the second NMI signal, microcomputer 3217 is againvectored into the NMI PROCESS. Here, the state of the FLAGS register isonce again checked. This time it is found to be equal to 1, therebysetting C3=1 and causing a jump, via the previously accessed programvector address, into the desired output function. Execution of theoutput function commences at this time.

Rather than discussing each output function in detail at this poibt, twofunctions--Single Frequency and Sequence Multifrequency--are chosen asrepresentative and are elucidated in the sequel. This selection allowsdiscussion of the significant considerations relating to signalgeneration as well as the situations in which FLAGS may take on thevalues of 2 or 3.

(III) SINGLE FREQUENCY FUNCTION

The flowchart of the program realizing this function is shown in FIG.95. This program generates a single tone from 1 Hz to 3200 Hz in 1 Hzincrements. The generation technique synthesizes a cosinusoidal waveformin the manner broadly described above in Section 2.2.1a with referenceto FIG. 19. FIG. 96 represents FIG. 19 recast for purposes of thepresent discussion.

Basically, normalized values of ±cos θ are stored in the ROM associatedwith microcomputer 3217, and different frequencies are produced bycycling through the ROM at different rates. The technique operates bykeeping the present phase, designated θ(n) for the nth phase samplewhere θ(n)=2πn/2^(L+2), in (J+2)-bit (J>L) phase accumulator 3206. Ateach sampling instant occurring at the rate f_(s) Hz, the value inaccumulator 3206 is used to index the table values in sample selector3213. Between sampling instants, the accumulated phase is incremented bythe J-bit frequency word, designated f_(w), received from PMU controller3100.

Since f_(w) is added to accumulator 3206 at the sampling rate f_(s), arelationship exists between f_(s), f_(w) and the output frequencygenerated, designated f_(o). The (J+2)-bit wide accumulator 3206 rotatesthrough 360 degrees at a rate

    f.sub.o =f.sub.w f.sub.s /2.sup.J+2.                       (3)

For example, if J=12 bits and f_(s) =2¹⁴ Hz, then f_(o) =f_(w). Greateroutput frequency resolution relative to f_(w) is possible by using alarger J-bit amount. For instance, if J=16 and all else remains thesame, then f_(o) =f_(w) /16. For the MLT system, the values are chosenso that there is a one-to-one correspondence between f_(w) and f_(o) ;thus f_(s) =2¹⁴ Hz and J=12.

Generation of cosinusoidal waves by sample selection requires that morethan two samples per cycle be produced or, equivalently, that the rateof sample production (f_(s) Hz) be at least twice the highest frequencygenerated. The rate of sample production for the illustrative embodimentof the MLT system has been set at 16.384 kHz (2¹⁴ Hz); this is more thanfive times the highest frequency (3200 Hz) to be produced. Programtiming is carefully controlled. Each program has exactly 1/4¹⁴ secondsin which to produce a sample. Since a machine cycle is equal to twicethe clock period of microcomputer 3217, that is, each machine cycle is2²¹ Hz, each program must take no more than 2⁷ =128 machine cycles toproduce the next sample. If a program step requires less machine time,then delay must be inserted. If a program takes more machine time, thena reduction in the upper frequency limit of 3200 Hz must occur, alongwith other complications to be explained shortly.

Referring again to FIG. 95, it is seen that the Single Frequencyfunction calls the SINCOS subroutine (designated by CALL SINCOS in FIG.95); this call sequence is also depicted in FIG. 86. The SINCOSsubroutine is a fast software realization of the table lookup technique.In this realization, accumulator 3206 of FIG. 96 is actually comprisedof one full byte (register 3211) and two partial bytes (registers 3210and 3212) of memory. Triple precision addition is used to add f_(w) toaccumulator 3206. The three-byte register arrangement allows the portionof the accumulator that is used as a sample selection index, that is,register 3211, to fall on a byte boundary. Also, since the frequencyword f_(w) actually comprises two bytes (F-hi and F-lo of FIG. 93),triple precision addition occurs by adding F-hi and F-lo, considered asone 12-bit addend, to registers 3210, 3211 and 3212, considered as a14-bit addend, with the sum being stored as a 14-bit result inaccumulator 3206. The memory arrangement is such that the four-highorder bits of F-lo align with register 3212, and all bits of F-hi alignwith register 3211. Finally, the two least significant bits of register3210 provide quadrant information, with `00` representing the firstquadrant, `01` the second quadrant, and so forth.

A flow diagram for the SINCOS subroutine is shown in FIG. 97. Once asample index and quadrant pointer have been determined in the callingprogram (in this case, Single Frequency), the correct sample value inone of two tables must be accessed. Indexing the appropriate table witheither the sample index directly or its complement yields the desiredsine or cosine value. As alluded to in Section 2.2.3a, each tablecontains 256 bytes of data values. One table has the values of +cos θthe other -cos θ. Both cover 0 to 90 degrees with 0.3516 degreesspacing. The values within the tables ar related by the two'scomplement. This relationship increases the speed of the subroutine andallows for frequency generation up to 3200 Hz since the computation timewhich would be needed to perform a two's complement operation on datafrom a single quadrant is eliminated. Once the sine and cosine valuescorresponding to a sample index have been attained, the proper sign isinserted and the samples are loaded into Port B (sine port) and Port D(cosine port). The proper sign is produced as follows: if the sample ispositive, shift right and "OR" with hex 80. If the sample is to benegative, shift right and "AND" with hex 7F. This produces an offsetbinary code from the two's complement table values which is directlycompatible with the format required by D/A converters 32142 and 32143 inring generator 3204 (see FIG. 85). It is apparent that while the 512table values are stored with 8-bit precision, the above steps of shiftright and prefix the correct sign actually results in 7-bits ofmagnitude precision.

It is helpful to note at this point that, besides accumulator 3206,there is a substantially identical accumulator (not shown) that isutilized whenever multitone output functions are requested. The secondsine/cosine generator, based on a second frequency word (f_(w2)), isnested within the SINCOS subroutine and is designated by SINCOS2 entrypoint in FIG. 97.

The assembly language program listed on pages 1-4 of Appendix A (this isthe same appendix as Appendix F of Rubin Ser. No. 399,177 illustratesone embodiment of a software implementation for the SINCOS subroutine.Cycle time through each quadrant is equal to 82 machine cycles. Anequivalent object listing of the SINCOS subroutine is embedded withinthe listing on pages 7-11 of Appendix A. Pages 7-11 provide the objectcode listing of all programs controlling microcomputer 3217. The objectcode for the SINCOS subroutine starts on page 11, line 2 with 0×18A5 andcontinues until line 11 and ends with 0×8160. For the Rockwellmicrocomputer utilized in the illustrative embodiment, the location ofROM begins at absolute hexidecimal address 0800; the SINCOS subroutinetherefore occupies addresses 0E7E through 0F0F inclusive.

The assembly language program listed on pages 5 and 6 of Appendix Apresents the software for implementing the Single Frequency outputfunctions. The machine cycle count for this program is 46 cycles. Anobject code listing of the Single Frequency Function is given as part ofthe listing in Appendix A. In particular, the code starting on page 9,line 5 with 0×A508 and continuing until line 9 and ending with 0×7D0B,between hexidecimal addresses B73 to BB4, is the pertinent object code.

(IV) SEQUENCE MULTIFREQUENCY FUNCTION

The flow diagram for the program realizing this function begins on FIG.98 and continues on FIG. 99. This program generates a sequence of timed,multitone cosine bursts within the 1 Hz to 2000 Hz band. A sequence ofup to 10 frequency pairs with a programmable duty cycle can be produced.

The reduction in upper frequency limit (3200 to 2000 Hz) is due to thelonger time needed to extract the pair of samples. The computation pathof the program requires 208 machine cycles to produce a sample. Thismeans that an output is available for strobing to the cosine D/Aconverter after 208 machine cycles rather than every 128 machine cycles.Thus, the sample rate at the converter output is effectively (208/128)16.384 kHz=10.08 kHz. Even though strobing occurs at a 10.08 kHz rate,microcomputer 3217 continues to operate at the 16.384 kHz rate. Fromsampling theory concepts, the samples of a cosine having a frequencyf_(w) and sampled at rate f_(s) are the samples of a cosine of frequencyf_(c) sampled at a rate

    f.sub.r =(f.sub.w f.sub.s)/f.sub.c, or f.sub.c =(f.sub.w f.sub.s)/f.sub.r.

Therefore, in order to utilize the existing ±cos θ tables, a scalingfactor is used to convert f_(w) to a value of f_(c) according to therelation ##EQU3## Since the scaling factor (208/128) is greater than 1,and the table values in conjunction with the low-pass filter arrangementare useful to a frequency of about 3200 Hz, f_(w) must be limited toapproximately 2000 Hz in the multitone generation arrangement.

In addition, since the factor (208/128) in equation (4) is not aninteger, f_(c) has a fractional part even though f_(w) is an integer.Thus, in binary, f_(c) requires more bits for its representation andthese additional bits fill the least significant bits of the F-lo byte(see FIG. 93). These four least significant bits are used during tripleprecision addition, but these, as well as the four most significant bitsof register 3212, are not used in selecting the sample index.

The conversion of the frequency number takes place in a subroutinecalled Convert Frequency; a flowchart of this program is shown in FIG.100.

With reference to the flow diagram of the Sequence Multifrequencyfunction in FIGS. 98 and 99, it is seen that once the program isentered, a check of the FLAGS register is initiated. The state of thisregister determines whether or not this is the first entry into theprogram. If entry has not been previously made, then the down-loadedfrequency bytes are converted through the Convert Frequency subroutine,the time-on flag is set and a frequency sequence counter is zeroed bythe Zero subroutine. A flowchart for the Zero subroutine is shown inFIG. 101. If entry has previously been made, then all registers andoutputs are initialized via the Zero subroutine and no output is, asyet, generated.

Both paths resulting from the FLAGS=1 test converge on a check of thesequence counter. This check determines if all the desired frequencieshave been generated. If they have not, then the frequency pointerincrements to the next frequency in the sequence. Once again, the FLAGSregister is checked to determine whether the T-ON or T-OFF subroutine isto be executed. The flow diagrams of FIGS. 102 and 103 represent theT-ON and T-OFF subroutines, respectively.

When the T-OFF subroutine is invoked (FLAGS=3), no output is generatedfor the specified time period. Once the off time has elapsed, theSequence Multifrequency program is entered again via the NMI PROCESS.All necessary checks are executed and the appropriate output is preparedfor generation. The T-ON subroutine is invoked whenever FLAGS=2. Also,since two frequencies are to be generated, the SINCOS subroutine isexecuted at both the SINCOS2 entry point level as well as at thesubroutine entry level. Cosine samples for both frequencies areextracted from the tables, added and then divided by two to maintainunity magnitude. The normalized cosine value is then loaded into thecosine port and strobed into cosine path D/A converter. Cosine samplescontinue to be generated for the specified on-time interval. Once thistime has elapsed, a NMI signal is generated and the sample generationceases. The program is reentered and the various checks done todetermine the next response. This sequencing continues until allfrequency pairs have been generated. Once the last pair is generated,output function execution halts and microcomputer 3217 resets (C3=0).

FIG. 104 indicates that the object code for the Sequence Multifrequencyoutput function is located at addresses CDO through CFD. The tabulardata in FIG. 104 presents the memory map for the output functions storedin ROM as well as the RESET and NMI processes and all subroutines. Inaddition, the assignment of storage in RAM, of input/output ports and soforth is also summarized in FIG. 104.

The Gain program (address B4E-B60) simplifies the gain alignment of themultiplying converters 32142 and 32143. Upon command, the program loadsPorts B and D with a binary zero. This value is then strobed into theconverters. When the converters respond to this value, their outputbecomes equal to their reference (multiplying) gain. If the output doesnot match the anticipated gain, a manual adjustment may be effected.

The Sample program (BC1-B6F) produces a sine and cosine value for apreselected sample index and is used for self-diagnosis.

The Sanity program (D28-E70) is used to check the internal registers,external counter/timer and computation of an internal memory check sumfor self-diagnosis. All internal registers are alternately loaded withones and zeros and then read back. If the retrieved value does not agreewith the loaded value, the "sanity" fails and reset is initiated (C3=0).If all registers pass, then the program sums all internal memory andcompares this to a known, stored value. A correct comparison results inthe internal counter being loaded with a predetermined count. Theexternal counter is then turned on and a software timer is started. Ifthe software timer times out before an NMI signal is generated, thensanity fails and C3 is set to zero. If an NMI signal is generated beforethe software timer becomes zero, then a check is made to insure that theNMI signal was not premature. When all checks have passed, PMUcontroller 3100 is notified via the handshaking protocol of the DataAccept subroutine.

The "Program Transfer Table Low" and "Program Transfer Table High"entries in FIG. 104 (addresses A00-A09 and A0A-A13, respectively)contain the low address byte and high address byte of the outputfunctions and Gain, Sample and Sanity programs. The "Inbyte Table" entrybasically summarizes FIG. 94. The "Initialization Index Table " containsinformation for initializing the input byte count.

Referring again to FIG. 84, source microcomputers 3215, 3217 and 3218all operate according to the same object code listed on pages 7-11 ofAppendix A. Information on the signals to be developed for the variousoutput leads 32021, 32022 and 32004 through 32007 is provided by PMUController 3100 via bus 31001. If leads 32021 and 32022 are presumed tocarry a signal denoted cos 2πf_(w), then, typically, lead 32005 alsocarries cos 2πf_(w) and lead 32004 carries sin 2πf_(w). It is possible,however, to phase offset the latter two signals from the former byloading accumulator 3206 of source 3204 with a nonzero initial valuecorresponding to, say, cos φ. Then the signals on leads 32005 and 32004become cos (2πf_(w) +φ) and sin (2πf_(w) +φ), respectively. The desiredoffset information is also provided by PMU controller 3100. Moreover, itis possible to have source 3217 develop signals having a frequency thatdiffers from the frequency of source 3217. Then, while leads 32021 and32022 may carry cos 2πf_(w), leads 32005 and 32004 may carry, say, cos2π(2f_(w)) and sin 2π(2f_(w)). In this way, harmonics on TIP and RINGmay be detected.

3.2.3a.2 DSG Hardware Considerations

Referring now to FIG. 18, the composite AC-DC signals used to energizeTIP lead 32002 and RING lead 32003 are supplied with summationamplifiers 3207 and 3208, respectively. Each amplifier 3207 or 3208 issupplied with an AC signal from generator 3202 and a DC signal from DCsource generator 3201. The accuracy and stability of all digital dataconversion in AC generator 3202 and DC signals derived in DC generator3201 depend upon a stable DC reference voltage found within generator3201. The device of the illustrative embodiment satisfying accuracy andstability requirements is a monolithic voltage regulator, number MC1723CL, produced by Motorola, Inc. and described in its "LinearIntegrated Circuits Data Book", dated December, 1972.

Suitable operational amplifier circuitry, coupled to the regulator,provides the various DC voltages required. The levels of the AC signalsalso derive from the regulator. The reference voltage produced by theregulator is translated to one of a finite number of levels (typically256) in a multiplying digital-to-analog converter (MDAC) of the typedeployed in AC generator 3202 (FIG. 84). The appropriate level to beselected is down loaded from PMU controller 3100. The output levelselected is supplied to MDAC's 32141 through 32145 of AC generator 3202via bus 32023. The digital sines and cosines are converted to analogform with the regulatorderived level to provide the desired signalstrengths. 3.2.3b Magnetic Current Sensor Circuitry

As already briefly discussed in Section 2.2.3b with reference to FIGS.20, 22 and 21, ring current-to-voltage converter 3402 providesmeasurement circuitry which is arranged to produce an output voltageonly when RING lead current is other than zero. The discussionhereinafter amplifies on the foregoing discussion with the aid of FIG.105; this figure combines the circuitry of FIGS. 20 and 21 which isessential to the operational description.

FIG. 105 depicts how two matched magnetic cores 3307 and 3308 areconnected to circuitry for measuring line current, designated I_(L),flowing on RING lead 33002 as a result of voltage impressed throughsource impedance 3309. Lead 33002 forms line winding L₁ on core 3307 andline winding L₂ on core 3308. Windings L₁ and L₂ are wound to produceessentially equal amounts of magnetizing field intensity (H) on cores3307 and 3308. For instance, if I_(L) flows from source impedance 3309towards the RING lead, then the field intensity is clockwise on bothcore 3307 and core 3308.

Ideally, cores 3307 and 3308 are of matching characteristics such thatthe hysteresis curves mapping flux density B versus field intensity Hfor each core are congruent. FIG. 106 depicts the upper-half of the B-Hcurve for core 1 (3307) and the lower-half for core 2 (3308) in verticalrelationship. Point 1 of core 1 indicates the intersection of the majorsaturation hysteresis loop on the B axis for a zero H filed. Point 1'depicts the similar intersection for core 2. If the cores aretemporarily presumed to possess identical charactristics and thewindings (L₁, L₂, C₁, C₂, S₁ and S₂ of FIG. 105) are not energized, thenthe flux densities are equal in magnitude for H=0. Points 1 and 1' mayalso be considered the quiescent points resulting from application andthen removal of field intensity. For example, if H_(L) represents thefield strength caused by current I_(L) flowing in line winding L₁, thenpoint 2 (point 2') depicts the new operating point on the B-H curve forcore 1 (core 2). Whenever I_(L) is reduced to zero, a minor saturationhysteresis loop is traced back to point 1 (point 1') to reestablishquiescent conditions. Because windings L₁ and L₂ are wound in the samedirections and the B-H characteristic is nonlinear, a change inoperating conditions between points 1 and 2 on core 1 causes acorresponding flux density change of ΔB₁ >0, whereas the same swingbetween points 1' and 2' causes a variation of ΔB₂ >0 on core 2. Thetotal overall change, designated ΔB, is defined as ΔB=ΔB₁ +ΔB₂. Theobjective of the current measuring circuitry of FIG. 105 is to force ΔBto zero using an appropriately fed back current, shown as current I_(S),which is derived from a voltage directly proportional to I_(L).

To derive the required voltage that supplies feedback current, cores3307 and 3308 have control windings C₁ and C₂, respectively, connectedto circuitry, as will be explained, whereby a succession of controlcurrent pulses causes current to flow in windings C₁ and C₂. Moreover,cores 3307 and 3308 have sense windings S₁ and S₂, respectively,connected to circuitry, as will be explained, whereby changes in fluxdensity may be electromagnetically detected.

Control winding C₁ is wound so that current flowing in the directionI_(C) in FIG. 105 causes a clockwise magnetizing field in core 3307.With reference to FIG. 106, current I_(C) causes the B-H curve to betraversed from point 1, through point 2 towards 3 whenever I_(L) iszero, or from point 2 to point 3 whenever I_(L), causing a field H_(L),flows. The measure of the field strength for movement along the B-Hcurve between points 2 and 3 is denoted ΔH. Control winding C₂ is woundso that current I_(C) generates a counterclockwise field strength incore 3308. Whenever I_(L) is zero, current I_(C) causes B-H curvetraversal from point 1' beyond point 3', whereas whenever a currentI_(L) flows, the path of traversal is from point 2', through point 1' topoint 3'. Again, ΔH is a measure of the field strength between points 2'and 3'.

Sense winding S₁ is wound so that for a current flow I_(S) as depictedin FIG. 105, a counterclockwise magnetizing field obtains in core 3307.On the other hand, I_(S) causes a clockwise magnetizing field in core3308. In steady-state operation, the field strength induced by currentI_(S) is to be equal and opposite the field strength due to currentI_(L) in each core 3307 and 3308. When this condition occurs, ΔB₁ =ΔB₂=0, thereby yielding ΔB=0.

Before steady-state operation is achieved, a transient period occurswherein a voltage is developed from alectromagnetic pick-up on sensewindings S₁ and S₂. As suggested above, this voltage drives currentI_(S). Since I_(S) cancels the effects of I_(L) in steady-state, thenthe developed voltage, designated V_(R), is proportional to RING currentin steady-state.

The transient period begins whenever I_(L) changes to a new valuerequiring measurement. For purposes of the immediate discussion, it isassumed a new I_(L) generates field strength H_(L) of FIG. 106. Pulsegenerator 34022 of FIG. 105 continually operates at about 50 kHz toproduce 55 percent duty cycle, unipolar, square-wave pulses. At theoutput of inverter 34022, the pulse is low for about 9 usec., allowingsufficient time for cores 3307 and 3308 to saturate from current I_(C)flowing from the positive voltage on lead 330042 through resistor340224. In FIG. 106, with I_(S) equal to zero initially, the coreoperating points move from points 2 and 2' to points 3 and 3',respectively, during saturation. The pulse is high for about 11 usec. toallow time for cores 3307 and 3308 to recover or flyback from thesaturation condition. During flyback, diode-zener diode pair 340223becomes conductive. As cores 3307 and 3308 return to operating points 2and 2', ΔB is generated. This differential flux induces a voltage on theseries-aiding sense windings S₁ and S₂. Since switch 34028 is closedduring flyback, this induced voltage is applied to the differentialinputs of high-gain amplifier 34021 through series resistor 34027.Capacitor 34024, which is connected between the output of amplifier34021 and its inverting input (-), in conjunction with amplifier 34021,form a voltage integrator. During the low interval of each pulse, switch34028 is opened and current I_(S) is provided to sense windings S₁ andS₂. The value of this current is determined by the voltage stored oncapacitor 34024 and the resistance of resistor 34023.

Over a succession of pulses from generator 34022, amplifier 34021 andcapacitor 34024 will cumulatively integrate successive voltages inducedon sense windings S₁ and S₂ so as to gradually change the output voltageof amplifier 34021, which appears on lead 34012. The voltage on lead34012 eventually achieves the steady-state value of V_(R), whereupon theamount of feedback signal cancels field H_(L) in core 1 and core 2. Atthis point, ΔB becomes zero and V_(R) is a measure of the amplitude andpolarity of current I_(L) which initiated the transient period. In theillustrative embodiment, the turns ratio of sense winding to linewinding and the value of resistance 34023 is chosen so that V_(R)=62.5I_(L) for V_(R) in mv and I_(L) in ma.

The description of this section has, to this point, presumed identicalcore characteristics for cores 3307 and 3308. In practice, ther exists aDC offset as well as dynamic offsets in core characteristics due to theinability of the cores to directly track, especially with temperature.The effect of the DC offset may be readily explained with reference toFIG. 107. In this figure, the top B-H characteristic is the same as thatdepicted for core 3307 in FIG. 106, that is, core 1. On the other hand,the bottom portion of FIG. 107 shows core 2 of FIG. 106 dashed, and theactual characteristic as a solid line. The disparity occurs because ofdrift. It is apparent that, even with H_(L) =0, a voltage proportionalto ΔB_(o) will be generated by the sense circuitry of FIG. 105. Tocompensate for the DC portion of this error, offset corrector 34025provides a small bias voltage which is converted to a small bias currentvia series resistance 34026 and supplied to the inverting input ofamplifier 34021. The voltage to be provided by corrector 34025 resultsfrom measurements on core pair 3307,3308 during a calibration periodwhich occurs at periodic intervals. During calibration, I_(L) is set tozero by opening leads 33092 and 330013 so that, in effect, the RINGpresents an open circuit and source driver 3302 (FIG. 20) isdisconnected. Voltage on lead 34012 of amplifier 34021 is then measuredas if a normal measurement was being processed. Since I_(L) =0, V_(R)should be zero. If V_(R) is not zero, then PMU 3100 feeds adjustmentinformation to corrector 34045 via bus 34052 emanating from detectorcontroller 3405 (FIG. 22). In the illustrative embodiment, corrector34025 is an 8-bit digital-to-analog converter. Thus the D/A output canrange over 256 steps corresponding to input codes of hexidecimal 00 toFF. At system startup, D/A corrector 34025 and amplifier 34021 arestatically set so that loading a midrange binary number into D/Acorrector 34025, typically hexidecimal 80 from corrector 34025, causesV_(R) to be zero. As drift occurs, this midrange number no longer zerosout V_(R), and another binary number is supplied to effect a zeroreading for V_(R). Since V_(R) (ma)=62.5I_(L) (ma), each step ofconverter 34025 corrects for an error of about 0.4844 mv/step.

Besides the first-order error described above in terms of a DC offset,there also exists a second-order effect that causes a so-called dynamicerror. This occurs when a finite impedance loads line windings L₁ and L₂even though driver 3302 is still disconnected. For instance, withreference to FIG. 20, it is possible to operate source impedance 3309and test termination 3310, via applique controller 3311, so thatwindings L₁ and L₂ are loaded with a test impedance-to-ground which isrepresentative of typical longitudinal-mode impedances expected of theloops under test. Because cores 3307 and 3308 exhibit different minorhysteresis saturation characteristics, a nonzero V_(R) may be measuredeven with corrector 34025 arranged to provide zero DC offset and eventhough I_(L) =0. One way to minimize the sensitivity of core pair3307,3308 to the wide range of impedances exhibited by the looppopulation is that of adding an inductor in series with windings L₁ andL₂. This inductor is chosen so that at the frequency used to switch corepair 3307,3308, that is, the frequency of operation of pulse generator34022, the loop impedance is small compared to the impedance of theinductor. In effect, core pair 3307,3308 is presented with a constantload at the pulse rate. On the other hand, the inductor must present alow impedance relative to the loop impedance over the range ofmeasurement frequencies so as not to isolate the loop from core pair3307,3308. The inductor is shown as element 3313 in FIG. 20 andtypically has a value of 300 μh. A corresponding TIP inductor 3312serves the same decoupling function for core pair 3305,3306.

Even with corrections for first- and second-order offsets, there isstill the potential for significant error whenever a minute current (ofthe order of 1 ua) must be measured. This situation typically occurs ina differential current measurement mode wherein, say, the TIP and RINGcurrents are essentially equal and the currents are routed through corepair 3305,3306 in opposing directions to measure TIP line current(I_(LT)) minus RING line current (I_(LR)) or I_(LT) -I_(LR). Indifferential measurement situations, the third-order error is removed byperforming an additional measurement. In this second measurement, therouting of both I_(LT) and I_(LR) through the apertures of core pair3305,3306 is reversed. Since the error mechanism provides a bias of thesame polarity to each measurement, the error is removed by subtractingthe two measurement results in PMU controller 3100 and then forming theaverage to obtain the correct output voltage.

Again with reference to FIG. 22, the output voltages proportional tocurrents flowing on the specific loop conductor arrangement appear onleads 34011 and 34021 of TIP converter 301 and RING converter 3402,respectively. Each of these voltages is processed in essentially thesame manner within detector 3400, so only the processing of the voltageV_(T) on lead 34011 is discussed in the sequel.

The voltage V_(T) is passed through analog filter 3403 to restrict thebandwidth of the measured current to 3200 Hz. The low-pass filterportion of filter 3403 is a conventional sixth-order low-pass filtercomprising three second-order sections in cascade. The passband is flatto within +1 dB, the =3 dB corner frequency is 3200 Hz and signals areattenuated by at least 30 dB at frequencies above 4000 Hz. Filter 3403also contains a 60 Hz notch filter that may be switched in-line or notdepending on the type of test in progress and the presence of excessive60 Hz noise influence on the loop under test. Normally the notch filteris on-line; PMU controller 3100, via detector controller 3405 and,particularly, the signal on line 34053, controls the insertion andremoval of the 60 Hz notch. The notch corner frequencies are 54 Hz and66 Hz and a 60 Hz signal is attenuated by at least 20 dB. The filteredoutput voltage V_(TF) from filter 3403 appears on output lead 34031.

The voltage V_(TF) is split into two paths and, thereby, serves asinputs to both AC gain unit 3408 and DC gain unit 3410. Gain unit 3408eliminates DC from voltage V_(TF) by a 10 Hz second-order high-passfilter with a -3 dB frequency of 4 Hz. Each gain unit 3408 and 3410 iscapable of providing either direct coupling to its output or aseparately programmable gain of four. Normally, gain units 3408 and 3410are set for maximum gain allowing for a peak current of 32 ma flowing onthe TIP before a 8.000 volt threshold for V_(TF) is exceeded.

Saturation detector 3406 has the outputs of gain units 3408 and 3410, onleads 34001 and 34003, respectively, as its inputs. Saturation detector3406 signals PMU controller 3100 that one or both voltage thresholdshave been exceeded. Detector 3406 is realized with absolute valuecomparator circuits on each of its inputs. Moreover, internal countercircuitry ensures that transient signals of less than 64 usecs. areignored and responses are triggered only by permanent overloads. An ACoverload condition is transmitted from detector 3406 via lead 34061 anda DC overload via lead 34062. The overload circuitry is of the latchingtype and, once tripped, remains in the logic state indicating overloaduntil cleared by PMU controller 3100. Leads 34061 and 34062 combine toform multilead 34005 emanating from detector 3400. The interruptoperation occurs as follows. As per FIG. 17, overload signals aretransmitted to measurement processor 3500, via lead 34005, and then toPMU controller 3100, via lead 35002. Acknowledgment of reception of theoverload signals and action to be taken is transmitted from PMUcontroller 3100, over bus 31001, to detector controller 3405 of FIG. 22.Any gain adjustments required are transmitted to the appropriate gainunits 3408 and 3410 via leads 34058 and 34057, respectively, and theclear signal to detector 3406 via multilead 34059. If the newlyattenuated signal still causes overload, then attenuator 3303 ofapplique 3300 (see FIG. 20) is switched into TIP lead 33001 to effect afurther reduction in the strength of the detected signal. The reductionis typically by a factor of four. The signal indicating that attenuator3303 is to be placed in-line is transmitted from PMU controller 3100 toappligue controller 3311 over bus 31001 and, finally, to attenuator 3303via multilead 33112. The TIP signals finally exiting detector 3400, onleads 34001 and 34003, are now within prescribed bounds and, if scaled,appropriate information as to scaling factors is stored in PMUcontroller 3100.

The signals on leads 34001 and 34003 serve as inputs to measurementprocessor 3500, as depicted in FIG. 23. The AC signal on lead 34001 issplit into three paths. One path directly connects to port 1 of the 7-1MUX in the upper-half of multiplexer 3501. The second path is one inputto multiplier 3701 and the third path drives an input to multiplier3702. The other inputs to multipliers 3701 and 3702 are the TIP(I) andTIP(Q) signals on leads 32007 and 32006, respectively. The operation ofmultiplier 3701, which is four-quadrant type AD 534 supplied by AnalogDevices, is exemplary of the operation of both multipliers 3701 and 3702and is now considered.

If the signal on lead 34001 is represented by

    r=A cos (2πft+θ.sub.1 +θ.sub.2)

where

f is the test frequency,

A is directly related to the current flow on the TIP lead [A=(62.5)I_(L) G, with G being 4, 1 or 1/4 depending on scaling],

θ₁ is a known phase shift due to magnetic current sensor and filtercircuitry and is determined periodically during calibrate procedures,and

θ₂ is an unknown phase shift due to reactance of the TIP lead,

and the signal on lead 32007 by

    s=cos (2πft+ν.sub.1),

then the output of multiplier 3701 is proportional to

    x=cos θ.sub.2 +cos [2π(2f)t+2θ.sub.1 +θ.sub.2 ].

As expected, the output x comprises a DC component and a doublefrequency component.

The output x serves as input to two filters 3510 and 3511. Filter 3510is a 10 Hz, second-order low-pass filter designed to remove the doublefrequency component, thereby passing only the DC term cos θ₂proportional to the conductance part of the TIP admittance. Typically,filter 3510 is utilized whenever the frequency of the signal on the loopis explicitly known.

Filter 3511 is employed whenever the frequency to be detected is unknownbut can be approximated, as with in-band signaling. In this case, 350Hz, second-order low-pass filter 3511 is used to reject the sumfrequency and pass the difference up to the expected maximum variance inthe uncertainity of the frequency.

The output of filter 3510 couples to port 2 of 7-1 MUX in the upperportion of multiplexer 3501, whereas filter 3511 connects to port 3. Theoutput of multiplier 3502, which is proportional to loop susceptance, isalso split to filter known and estimated frequencies via low-passfilters 3512 and 3513. These latter two filters are substantially thesame as the former filter pair 3510 and 3511. Ports 4 and 5 of upper 7-1MUX in multiplexer 3501 receive the outputs from filters 3512 and 3513,respectively.

The broadband output voltage on lead 34003 provides the remaining twoinputs to upper 7-1 MUX in multiplexer 3501. Port 6 is directly coupledwhereas port 7 receives the output of 10 Hz, second-order low-passfilter 3514. The input to filter 3514 is the voltage on lead 34003 sofilter 3514 performs the DC isolation. Port 6 is used for broadbandnoise measurements.

The voltages on RING leads 34002 and 34004, which are the counterpartsof TIP leads 34001 and 34003, supply signals to the lower-half 7-1 MUXin multiplexer 3501 in the same manner. The function of multiplexer 3501is that of selecting corresponding ports in its upper and lower 7-1MUX's and connecting the signals arriving at the selected ports tosample-and-hold (S/H) circuits 3504 and 3505, respectively. Selection ofthe desired interconnection from input-to-output in multiplexer 3501 isunder control of measurement interface 3508, via busses 35082 and 35083,respectively. The interconnect information is transmitted to interface3508 from PMU controller 3101 on bus 31001. Multiplexer 3501 is enabledvia two conductors forming part of multiple lead 35071 interconnectingcontroller 3507 with interface 3508. Enabling information is initiallytransmitted, via bus 31001, to controller 3507 for decoding. In thepreferred embodiment, each of the upper and lower halves of multiplexer3501 is standard device DG 508 supplied by Intersil Corporation.

The voltages selected for processing appear simultaneously on leads35011 and 35012 from multiplexer 3501. Circuits 3504 and 3505 are unitygain S/H devices; lead 35073 from measurement controller 3507 puts theS/H devices in the hold mode. The sampled outputs appear on leads 35041and 35051, and these leads serve as inputs to 2-1 MUX 3506. The sampledsignals are routed, one at a time, through MUX 3506 to programmable gainamplifier (PGA) 3502 over lead 35061. A logic signal on lead 35074linking measurement controller 3507 with MUX 3506 determines whichsampled signal is to be routed to PGA 3502 for amplification; the timingof this logic signal will be examined shortly.

The four remaining circuit blocks of FIG. 23 not yet discussed, namely,PGA 3502 A/D converter 3503, measurement interface 3508 and measurementcontroller 3507, cooperate to perform the unitary operation of providinga series of 20-bit digital words to DSP 3600 of FIG. 17. As such, thesecircuits are highly interactive and critically timed. Initially, then,the discussion focuses on the basic function performed by this circuitgroup without concern for circuit details. Subsequent discussionelaborates on circuit details, where necessary, to complete thedescription.

The instant discussion commences with reference to the timing diagram ofFIG. 108. The upper trace in FIG. 108, designated Trace 1, depicts anegative-going pulse that serves as the "time zero" reference point. Thepulse of Trace 1 initiates the production of one series of 20-bit wordsand the other thirteen traces of FIG. 108 indicate the unfolding ofevents for the first two words; remaining word pairs are processedsimilarly. Trace 1 is a "sample request" pulse transmitted from PMUcontroller 3100 over one conductor of bus 31001 of FIG. 23. A onemegahertz signal is obtained as a result of a signal provided over asecond conductor of bus 31001 to provide timing in multiples of 1 usec.The sample request pulse illustrated is generally one from a series ofpulses transmitted whenever a series of data words is to be supplied forprocessing. Possible pulse rates include 100 Hz, 2000 Hz or 8000 Hzdepending on the type of signal processing to be effected. The samplerequest pulse is transmitted after source generator 3200 is started,notch filters 3403 and 3404 have been switched in or out, gain units3408-3411 have been set, and so forth and after a settling time ofapproximately 50 milliseconds has elapsed.

The negative-going edge of the pulse of Trace 1 triggers a state timingcircuit. The states and the duration of each state are depicted by Trace2. The initial state, designated State 0 (S0), lasts 30 usec.; the nextstate, called S1, consumes 4 usec.; S2 is of 12 usec. duration; and soforth. Progression through the thirteen states S0, S1, . . . , S5, S6,S1, . . . , S5, S7, requires 234 usecs. This cycle is utilized wheneverin-phase and quadrature sample pairs are required, typically at the 100Hz rate. If only a single in-phase sample is required, the cyclecomprises seven states S0, S1, S2, S3, S4, S5 and S7 and is completed in118 usec. Since a pulse rate of 8000 Hz is equivalent to sampleproduction at a 125 usec. rate, then only a sequence of single samples,rather than sample pairs, can be produced at the 8000 Hz rate. For thepurposes of the immediate discussion, it is presumed that a sequence ofsample pairs is to be produced; this request is transmitted over databus 31001 from PMU controller 3100 to measurement controller 3507.Signals indicating the presently active state--S0, S1, . . . , orS7--appear on bus 35072 of FIG. 23.

Trace 3 indicates the signal appearing on lead 35074 used to drive MUX3506. A "low" on lead 35074 connects the output of S/H 3504, on lead35041, to MUX 3506 whereas a "high" connects S/H 3505 to MUX 3506. The30 usec. spent in S0 and the 32 usec. in S6 allows PGA 3502 time to slewdown and settle before an analog-to-digital conversion commences in A/D3503.

Prior to initiating a set of measurements via A/D 3503, it is possiblethat AC or DC saturation signals, arriving on leads 34005 and 34006 atthe input to measurement controller 3507, may cause an interrupt pulseto be generated. This pulse is transmitted to PMU controller 3100 onlead 35002 and causes the state generator to remain in S1. The offendinggain unit (3408-3411 of FIG. 17) is reduced in gain or the appropriateattenuator (3303 or 3304 of FIG. 20) is switched in-line to alleviatethe saturation condition, as discussed earlier. State 0 is reestablishedand the complete measurement cycle begins anew. Reset to S0 istransmitted by DSP 3600 over one conductor of bus 36001. Trace 14indicates the timing of the saturation interrupt signal.

Presuming saturation has been eliminated and 30 usec. has elapsed, S1 isnow activated and measurements may begin. Each in-phase and quadraturesignal is measured twice; the first establishes the gain range and thesecond performs the actual measurement. The measurements are initiatedby the signal of Trace 4, which depicts a so-called "A/D start" signalon lead 35085. One A/D start signal is timed to begin on the trailingedge of the S1 pulse whereas the other is synchronized with the end ofS3. Each A/D start pulse lasts about 2 usec., and the trailing edgetriggers an actual analog-to-digital measurement in A/D 3503. An actualmeasurement requires a maximum of 10 usec., so a measurement iscompleted before the end of S2 or S4. A/D converter 3503 is a successiveapproximation device and produces a serial data output one on leadsynchronized by thirteen clock pulses on another lead. These pulses areillustrated in Trace 5, which depicts the twelve data bits on oneconductor of multiple lead 35031 combined with the first or synch pulseon the clock conductor of lead 35031. During the last 10 usec. of S2,the number of leading zeros present in the data pulses are counted. Thisinterval is depicted by Trace 6. Leading zeros are generally anticipatedbecause the gain of PGA 3502 is small initially.

The gain of PGA 3502 is now reset based upon the number of leading zeroscounted. This allows the full range of A/D 3503 to be utilized formaximum resolution of the signal being measured. The 32 usec. allocatedto S3 affords the necessary adjust period in which the desired gainsetting is transmitted to PGA 3502 and settling occurs. Trace 8 depictsthe intervals in which the gain of PGA 3502 is adjusted from thestarting value; this occurs during the "high" state wherein theappropriate gain data is transmitted over bus 35084.

For some digital filtering programs within DSP 3600 (see FIG. 17), it isdesirable to incorporate zeros in the two least significant positions ofa data word. This avoids a phenomenon called a "limit cycle", as will bedescribed when DSP 3600 is discussed. In those situations requiringtrailing zeros, PMU 3100 signals measurement interface 3508, via bus31001, that so-called "psuedo-gain" is to be supplied. However, if thereare less than two leading zeros in the data word upon the completion ofthe gain range measurement, that is, State 2 of Trace 5, thenpsuedo-gain may cause saturation. When this situation occurs, aninterrupt is transmitted to PMU controller 3100, via lead 35002, and thestate of the processing remains disabled in S3. DSP 3600 sends a resetsignal on bus 36001 to begin the entire cycle again by returning toState 0 and pseudo-gain is disabled via a signal on bus 31001. Thesignal depicted by Trace 7 indicates the timing of the interrupt andrestart as a result of the condition referred to as "pseudo-saturation".

Presuming there is no saturation due to psuedo-gain, the second pulse ofTrace 4 indicates the second A/D measurement commences 2 usec. into S4.However, another interrupt condition may override this secondmeasurement, and this is represented by Trace 13. If DSP 3600 is notready to accept data because, primarily, it is still processing pastdata, a signal to this effect is transmitted over lead 36002. If thissignal is present at the end of S3, an interrupt pulse is sent frommeasurement controller 3507, via lead 35002, to PMU controller 3100. Thestate generator latches into S4 until reset to S0 indicating a repeat ofthe entire cycle is required.

If it is assumed that DSP 3600 is ready to accept data, the results ofthe second measurement, depicted as occurring during S4 by Trace 5, aresent to measurement interface 3508 on one conductor of lead 35031emanating from A/D 3503. Traces 9, 10 and 11 indicate the sequence ofevents occurring during S5. As per Trace 9, a synchronizing pulse istransmitted to DSP 3600, via one conductor of multiple lead 35001emanating from measurement interface 3508, indicating data is ready tobe transmitted. Trace 10 shows 24 usec. time windows in which DSP 3600is "clear-to-read" A/D data; a "low" clear signal is transmitted overanother conductor of lead 35001. Finally, Trace 11 depicts the timing of20-bit data words to DSP 3600 via a series of pulses over a thirdconductor of lead 35001. The data word itself is transmitted on a fourthconductor of lead 35001 in synchronism with the pulses of Trace 11.After 20 bits have been received, an "input buffer full" signal istransmitted from DSP 3600 to measurement interface 3508 in order todiscontinue transmission of the data. This buffer-full signal isillustrated by Trace 12 and appears on lead 36002.

Multiple conductor leads 35071 and 35081 convey appropriate signalsderived in measurement controller 3507 to measurement interface 3508 andvice versa, respectively. The signals on lead 35071, besides the enablesignals described earlier, include overall timing information, reset toState 0 pulse and request for "psuedo-gain". The signals on the twoconductors of lead 35081 indicate that DSP 3600 is not ready to receivedata and the psuedo-saturation condition enabling interrupt of PMUcontroller 3100.

Focusing now on circuit particulars, FIG. 109 depicts circuitryimplementing an illustrative embodiment of PGA 3502, which enablesautoranging during measurements of the signal on lead 35061. Twomeasurements of a given signal are taken, namely, one with the gain ofPGA 3502 set at 1.18 and the second with a gain, expressed in powers oftwo, such that the maximum possible signal delivered to A/D converter3503 via lead 35021 does not exceed its input rating. The high gainenables higher resolution by converter 3503 because a greater number ofhigher order bits will be significant. The amount of gain added isdetermined by the number P of leading zeros from the first measurement;the gain is 2^(P), P≦8. Information about the detected value of P istransmitted from measurement interface 3508 (FIG. 23) over bus 35084,which serves as input to PGA decoder 350205.

Bus 35084 comprises five digital lines I1, I2, I4, I8 and I0. During thefirst measurement, I0 is a logic 1 and the other four lines are ignored.However, the logic states of lines I1, I2, I4 and I8 determine theamount of gain added during the second measurement when I0 is logic 0and is basically ignored. For instance, if P=5 as a result of the gainrange measurement, then I4 and I1 are logic 1 with I8 and I2 at logiczero. Decoder 350205 translates logic information on bus 35084 to a setof decoded states D0, D1, . . . , D10 wherein only one state in therange D5 through D9 is energized at any time and similarly for states D0through D4 in combination with D10. Decoded states D0-D10 control theoperation of switch-divider networks 350202 and 350204, which are in thefeedback path of operational amplifiers 350201 and 350203, respectively.By selectively switching in and out high precision resistors undercontrol of states D5-D9, network 350204 sets the gain of amplifier350203 and similarly for network-amplifier pair 350202,350201. Forinstance, with state D5 activated, the gain of amplifier 350203 is one,D5 corresponds to a gain of 2; and so forth. Tables summarizing thisdiscussion are as follows:

    ______________________________________                                        AMPLIFIER 350201                                                                            GAIN IN STATE                                                   I0   I8    I4      I2  I1   D0  D1   D2  D3    D4  D10                        ______________________________________                                        1    --    --      --  --                          1.18                       0    0     0       0   0    1                                                 0    0     0       0   1        2                                             0    0     0       1   0        2                                             0    0     0       1   1             4                                        0    0     1       0   0             4                                        0    0     1       0   1                 8                                    0    0     1       1   0                 8                                    0    0     1       1   1                       16                             0    1     0       0   0                       16                             ______________________________________                                    

    ______________________________________                                        AMPLIFIER 350203                                                                               GAIN IN STATE                                                I0    I8    I4      I2  I1     D5  D6    D7  D8    D9                         ______________________________________                                        1     --    --      --  --     1                                              0     0     0       0   0      1                                              0     0     0       0   1      1                                              0     0     0       1   0          2                                          0     0     0       1   1          2                                          0     0     1       0   0                4                                    0     0     1       0   1                4                                    0     0     1       1   0                    8                                0     0     1       1   1                    8                                0     1     0       0   0                          16                         ______________________________________                                    

The first measurement is made with a gain of 1.18 to protect againstswitching in too high a gain during the second measurement andoverloading A/D converter 3503 (FIG. 23). Thus the signal on lead 35061is considered to be 18% higher than its actual value to reduce theactual amount of gain added. This alleviates an overload situation thatmay be exemplified as follows. It is supposed there is no 18% margin andthe output of converter 3503 on the first measurement is 0011 1111 1111or decimal 32527. This is just below the 0100 0000 000 or 36623 decimallevel. With one leading zero, the gain is 2. If the second measurementwas taken with a preturbation due to noise, the additional gain wouldcause an overflow. This results in an erroneous measurement and the testwould be rerun. The margin of 18% includes a 13% allocation to the largestep difference (36623=1.13×32527) and 5% to other circuit tolerances.

A third amplifier stage comprising operational amplifier device 350206,inverting input resistor 350207, and RC parallel feedback combination350208 and 350209 provides level shifting and filtering. Resistor 350207has value αR so that the magnitude of the gain of this last stage is1/α. The value of α is determined as the ratio of the maximum signalallowed on input lead 35061 to maximum of the signal on output lead35021 for low frequencies. In the illustrative embodiment, α=8/5.resistor 350208 and capacitance 350209 act as a first order low-passfilter with a cutoff of about 30 kHz; this bandwidth is sufficient toallow PGA 3502 to slew and settle within 32 usec., yet is narrow enoughto reject high frequency noise. Moreover, operational amplifiers 350201,350203 and 350206 have a high gain-bandwidth product and low offset. Inthe illustrative embodiment, operational amplifiers 350201, 350203 and350206 are device LF 156 manufactured by National Semiconductor. Inaddition, A/D converter 3503 (FIG. 23) is manufactured by Burr-Brown andsold under the code ADC85.

3.2.3c Digital Processing and Control

As depicted by the rightmost diagram in FIG. 58 and in view of thememory partitioning shown in FIG. 68 for PMU 2102, PMU controller 3100and DSP 3600 are mutually dependent subsystems so it is advantageous, atthis juncture, to discuss their implementations within the same context.

As alluded to above in Section 3.2.1 when LTS controller 2000 wasdiscussed, PMU main controller 3145 and LTS main controller 2045, bothdepicted in block diagram form in FIG. 58, have substantially the samecircuit realizations. LTS main controller 2045 is the one depicted byFIG. 59 and discussed in detail with reference to FIGS. 60-65. PMU maincontroller 3145 is realized by incorporating four minor variations inthe circuitry of FIG. 59. These include the reassignment of status leadsGPIB0-GPIB2 of adapter 2020, the selection of a different clock signalsat the output of clock divider 2005, the reprogramming of decoder 2015and, finally, the replacement of RAM1 memory 2042 with PROM. Withrespect to the status leads, if PMU controller 3100 forms a part of PMU2101, then GPIB0 and GPIB2 are both connected to logic 0 and GPIB1 isconnected to a logic 1. In a similar manner, PMU 2102 has status leadbits of `011`, whereas PMU 2103 shows a bit arrangement of `100`, wherethe first bit is GPIB0. Since PMU's 2101-2103 are connected to bus20001, these unique status lead identifiers allow for unambiguoustwo-way communication. With regard to outputs from clock 2005, both CLKAand CLKC remain the same (15.625 kHz and 62.5 kHz, respectively) butCLKB becomes 500 kHz. Regarding memory accessing, PROM 2016 of decoder2015 has 0xFF in all addresses except the following: 0x70 and 0x71 have0xE7; 0x72 and 0x73 have 0xEB; 0x74 and 0x75 have 0xED; 0x76 and 0x77have EE; and both 0x7A-0x7F and 0xFA-0xFF, have, respectively, hex dataCF, CF, 3F, BF, BF, 6F. Finally, the four 2K×8 devices furnishing RAM12042 of FIG. 64 are replaced with 4K× 8 2732A-type PROM's by providingLAB11 as an input in place of LWR* and grounding A5 of device 2016. Thistotal of 16K of ROM becomes BANK E as shown in FIG. 68. BANK A2 isprovided by RAM2 2043, as it was for LTS main controller 2045; BANKS A3and A4 are 8K of addressable I/O space associated with PMU maincontroller 3145 of FIG. 58. Of the five remaining memory banks, BANK A,BANK B and BANK C are provided by universal memory 3150 and BANK D andBANK A1 are provided by DSP circuitry 3600.

As also indicated above, in the discussion of Section 3.2.1b with regardto universal memory 2050, it was pointed out that the basic memoryimplementation would also be utilized for PMU controller 3100. This isdepicted in FIG. 58, wherein bank memory 3150 and PMU main controller3145 cooperate to form PMU controller 3100. Bank memory 3150 is alsodepicted, in block diagram form, by FIG. 69 and in detail by FIGS. 70and 71. However, since BANK A now comprises 32K bytes and BANK B andBANK C only 16K bytes each (as compared to three 20K bytes segments forLTS controller 2000), PROM's 2054-2055 of FIG. 70 are programmed so thatMCS0*-MCS7* select BANK A, MCS8*-MCS11* select BANK B and MCS12*-MCS15*select BANK C.

The remaining three memory segments of FIG. 68, namely BANK A1, BANK A3and BANK D, are either provided by or allocated to DSP 3600. Theimplementation of DSP 3600 in the preferred embodiment is shown in blockdiagram form by FIG. 110. ROM 3610, shown in detail in FIG. 111,comprises four 4K×8 PROM's; this total of 16K bytes of memory serves asBANK D. Also shown in FIG. 111 is RAM 3615, which comprises eight 4K×1static RAM's serving as BANK A1. The arrangement of FIG. 111 isbasically the same as that depicted in FIG. 73 for LTS main controller2045 and may be implemented in the same manner.

Of the final 4K of memory space remaining to be discussed, that is, BANKA3 which is assigned locations 0xE000-0xEFFF, the 1K from 0xEC00-0xEFFFis assigned to dual-port RAM (DPR) 3620, including devices 3621-3627, ofFIG. 112. Memory 3620 functions for PSP 4000 as ROM memory, but withrespect to PMU controller 3100, this same memory space appears as RAM.This allows PMU controller 3100 to store processing programs in its ROMand by downloading to locations 0xEC00-0xEFFF, any necessary filteringor processing functions can be performed. This feature is includedbecause the special purpose processor implementing PSP 4000 can onlyaccess 1K of memory. Although each processing program is, by itself,less than 1K, it is necessary to include this feature so that aselection of algorithms is available for downloading depending on theanalysis required. Moreover, this 1K is 16 bits wide rather than the 8bits discussed to this point. As witnessed in FIG. 112, devices3621-3624, each of which is 1K× 4, are grouped in pairs to provide theupper byte (devices 3623 and 3624) and the lower byte (devices 3621 and3622) of the 16 bit words. Devices 3621-3624 are, typically, type 40Asupplied by the Western Electric Co.

Buffer transceiver 3625 in FIG. 112, a LS244 furnished by the WesternElectric Co., interfaces address leads RAB00-RAB07 to dual-port RAMdevices 3621-3624. The eight outputs DAB0-DAB7 from transceiver 3625,when combined with buffered versions of RAB08 and RAB09, that is, DAB8and DAB9, provide ten address leads for one-in-1024 memory locationdecoding. These address leads select a unique memory location in RAMdevices 3621-3624 when enabled by the RAM* signal. Bus transceivers 3626and 3627, types LS245, interface internal data leads DB0-DB7 to RAMdevices 3621-3624. In particular, transceiver 3626, when operated inconjunction with WE* and CE* of devices 3621 and 3622, stores 8-bit datainto devices 3621 and 3622. Similarly, transceiver 3627 directs 8-bitdata to devices 3623 and 3624. In this way, the program desired for aparticular test request can be downloaded into devices 3621-3624.Transceivers 3625-3627 comprise one access port, designated Port A, toDRP 3620. With the four 1K×4 RAM's loaded with the program of interest,transceivers 3625-3627 may be deactivated and demultiplexing section3630 activated to access the desired program.

Demultiplexing section 3630, comprising four LS374 flip-flopsimplementing gates 3631-3634 and buffer 4002 (a component comprising PSP4000 as discussed shortly) directs the addressing and accessing ofinformation stored external to PSP 4000. Gates 3621-3624 comprise thesecond port (Port B) of DPR 3620. During each processor cycle of PSP4000, four memory addresses are generated. When external ROM isutilized, as in this illustrative embodiment, two of the addresses areavailable to external devices via leads DBS0-DBS15 emanating from buffer4002. Then, during a typical cycle: gates 3631 and 3632 latch the firstaddress generated, which is the address of an instruction, whereas gates3633 and 3634 latch the instruction itself by reading the bitconfiguration on leads DDB0-DDB15 associated with devices 3621-3624; thenext address generated selects a coefficient in essentially the samemanner, that is, gates 3631 and 3632 first capture the 10-bit addressoff bus DBS0-DBS15, and then gates 3633 and 3634 transmit the latchedcoefficient bits onto the same bus during a later portion of the cycle.(The remaining two addresses that are generated direct data read and adata write to memory internal to PSP 4000).

A 28L22 type device, shown in FIG. 113 as device 3641, is the primarymeans for address decoding within decoder 3640. Decoding is accomplisheddown to the 4K granularity level to provide the K0*-K4* decode signals.Further chip-select address decoding is accomplished by using discretelogic in combination with dual 2-4 decoder 3642, a LS139 type device.Also serving as an input to decoder 3640 is bank switching lead RMBDwhich, when low, allows the memory space in the range 0x8000 to 0xBFFF(BANK D) to be addressed. The coding of fuseible link PROM 3641 is asfollows: all memory locations contain 0xFF except 0x10-0x17 whichcontain, respectively, BE,BE,BD,BD,BB,BB,B7,B7 in hex (similarly for0x30-0x37, 0x50-0x57 and 0x70-0x77), 0x58, 0x59, 0x5C and 0x5D, whichcontain AF,AF,DF,9F in hex (similarly for 0xD8, 0xD 9, 0xDC and 0xDD),and 0x78, 0x79, 0x7C and 0x7D, which contain AF,AF,9F,9F in hex(similarly for 0xF8, 0xF9, 0xFC and 0xFD).

Also included in FIG. 113 is reset logic 3650 which generates the resetsfor the associated PMU's 2101-2103. Parallel D flip-flop device 3650, atype LS174, forms the basis of the reset realization. The resetsprovided are ORST* (output reset) at bit 0 of address 0xE400, TRST*(test reset) at bit 1 and ARST* (acquisition reset) at bit 2.

The latch circuitry comprising devices 3691-3695 in FIG. 114 resides inthe DSP I/O memory space shown as BANK A3 in FIG. 68. In particular,latch 3691, a LS273, is associated with address location 0xE803. Thedata bits at this address have the following meanings: bit 7--if thisbit is low, and PMU controller 3100 addresses memory between 0xEC00 and0xEFFF, then the lower eight bits of dual-port RAM 3620 are enabled viaTSCL. Otherwise, the upper eight bits are enabled via TSCH; bit 6(DSPMEM)--when this bit is low, the chip select leads on demultiplexergates 3631-3634 are enabled; bit 5 (EXM*)--when this bit is low, allinstructions for PSP 4000 are fetched from the external address/data busEBR. In the illustrative embodiment, it is always low; bit 4 (CTS*)--ahigh on this bit inhibits outputs from DSP 3600. This bit is used tosynchronize transmissions from PSP 4000 to PMU 3100; bits 2 (CO) and 1(C1)--C1 is used for framing purposes during outputs from PSP 4000 andCO is used to demand outputs from PSP 4000.

In view of the above information, the operation of Ports A and B of DPR3620 may be summarized as follows. PMU controller 3100 writes into DPR3620 by setting DSPMEM high. The desired upper-half or lower-half of DPR3620 is chosen by seting bit 7 of address 0xE803 appropriately. Theselected half may then be accessed by addressing locations from 0xEC00to 0xEFFF. Since DSPMEM is high, the appropriate CS[ ] and TSC[ ]signals are active low, depending on the sense of bit 7. In order forPMU controller 3100 to allow access through Port B, DSPMEM is set low.In addition, EXM* is always low. Then PSP 4000 may be signalled to startits processing. The EXE* and CLKOUT signals generated in device 4002demultiplex the external 16 bit address/data leads emanating from PortB.

DRP 3620 provides more than a means for expanding the number of programsthat PSP 4000 may execute. The program that is downloaded from PMUcontroller 3100 may be modified in a limited manner by changing datastored in DPR 3620 prior to execution by PSP 4000. The reason for suchmodifications was discussed in Section 2.2.3d with reference to changesto primitive table default values.

Devices 3693-3695, all being of the type 41KP furnished by the WesternElectric Co., form a serial to parallel latch for a 20 bit output. Theyare accessible at address locations 0xE804-0xE806, respectively. Thefour most significant bits at address 0xE804 are the four leastsignificant bits in the 20 bit output word from PSP 4000; bits 4-11 and12-19 of the output word reside at 0xE805 and 0xE806, respectively.

Address location 0xE807 is buffered by latch 3692, a LS367 type devicefurnished by the Western Electric Co., and is used to read outputsignals from PSP 4000. Bit 4 (OBE) on latch 3692 indicates that anoutput is available from PSP 4000 when the bit is low. Bits 1 (S1) and 2(S2) provide scaling information during an output cycle.

Any further discussion with respect to the portion of programmablesignal processor 4000 shown in FIG. 114 as element 4001 is deferred tothe next section so that the mathematical basis presented at the openingof that section may be integrated with the discussion of the varioussubcomponents comprising PSP 4000.

3.2.3d Digital Processing Considerations

Before continuing with the description of the illustrative embodiment ofthe present invention and, in particular, PSP 4000, it is informative tofirst consider one theoretical basis for the discrete-time processingtechniques to be discussed in this section. This basis providesadditional insight and allows for a full elucidation of the subjectmatter of the illustrative embodiment.

(The following discussion summarizes filtering concepts pertinent tosignal processing in the MLT system. A thorough exposition of thedigital processing field is contained, for example, in the text "DigitalSignal Processing", by A. V. Oppenheim and R. W. Schafer and publishedby Prentice-Hall in 1975). In the art of discrete-time filtering,certain classes of filters may be represented by a linear differenceequation (LDE) with constant coefficients: ##EQU4## where {x(n)} is aninput sequence;

{y(n)} is an output sequence;

a(k) and b(j) are fixed, real constants for each k and j, respectively;and

N and L are integers

The elements x(n) and y(n) are not, in general, limited to a specificset of values, but may have a range defined over the real (or evencomplex) numbers. If the elements are limited to a specific set ofvalues, the filtering is then referred to as digital filtering.

For purposes of the present invention, the input sequence generallyarises from sampling a continuous time function x(t). The term"discrete-time" implies that the independent variable, time, is definedfor only a discrete set of values (for example, n/100 for 100 Hz samplerate or n/8000 for 8000 Hz sample rate). Basically, then, thediscrete-time filter of equation (5) linearly transforms one set ofsample values or input sequence elements to another set of sample valuesor output sequence elements.

Again with respect to equation (5), certain other observations arepertinent: (i) y(n) is determined by only past elements of the outputsequence so that equation (5) may be solved recursively; on practicalgrounds, this makes the system realizable in that present outputelements do not rely on future otuput elements; and (ii) y(n) isdetermined by only present and past input elements so that real-timeprocessing is possible, that is, all necessary processing can beaccomplished during the interval between samples.

Two important cases of sampled data filters may be distinguished. Thefirst is the so-called nonrecursive case which is obtained when all b(j)are zero in equation (5) (and, of course, at least one a(k) is notzero). The second is the recursive case which is obtained when at leastone b(j) is not zero and at least one a(k) is not zero.

Focusing on the nonrecurisve case, as exemplary, equation (5) may berewritten to yield: ##EQU5## where h(k) has been substituted for a(k)and N has been replaced by N-1, that is, the filter is of length N. Theset of elements h(k) is the impulse response of the nonrecursive filterand the form of equation (6) demonstrates that any output element isdetermined by the convolution of the impulse response elements with theinput sequence elements. Similar remarks also apply to the recursivefilter case, but the relation between k(k) and the a(k) and b(k)coefficients is not as straightforward as in the nonrecursive case.

Often it is advantageous to consider sequences and sequencemanipulations from the viewpoint of a transform domain. This isparticularly true in the case of a convolutional operation involvingsequences since the operation may be converted to multiplication oftransforms.

The transform most often utilized when dealing with sequences is thez-transform, where z is a complex variable. For a general sequence{f(n)}, the z-transform is given by ##EQU6## In general, the summationof equation (7) coverges over a certain region in the z-plane, thisregion being called the region of convergence (ROC). For sequenceshaving a ROC including the unit circle in the z-plane (that is, a circleof radius one centered at the origin), then the transform may be writtenas F(e^(j)ω). This obtains by substituting z=e^(j)ω in equation (7)since e^(j)ω is the expression for the unit circle in the z-plane; theexpression F(e^(j)ω) is called the Fourier Transform of the sequence.

One important property of this Fourier Transform is its periodic nature,that is, the sequence transform repeats in ω-multiples of 2π, presumingthe input signal is sampled at a normalized rate of one second. If theinput signal is sampled at a rate ΔT seconds, then the Fourier Transformrepeats in multiples of 2π/Δt.

Another property, mentioned earlier, is the conversion of a convolutionin the sequence domain to a multiplication in the transform domain;thus, equation (6) may be written as Y(e^(j)ω)=H(e^(j)ω)X(e^(j)ω) whereX(e^(j)ω), Y(e^(j)ω) and H(e^(j)ω) are the Fourier Transforms of theinput sampled signal, the output sampled signal and the impulseresponse, respectively. This conversion provides insight since it isgenerally easier to conceptualize multiplication instead of convolution.

Yet another property of the sampling operation is that sampling of acontinuous time signal at a particular clock rate causes thecontinuous-time spectrum of the signal to appear as sidebands about theclock frequency and all harmonics of the clock frequency.

Using z transform techniques, it is possible to express equation (5) inthe form

    Y(z)=H(z)X(z),                                             (8)

where X(z), Y(z) and H(z) are the z transforms of the input, output andinpulse responses. H(z) is generally referred to as the transferfunction of the particular filter characteristic and typically comprisesa number of poles and zeros in the z plane. In the design ofhigh-performance discrete filters, placement of the poles and zeros ofthe transfer function at any location in the z plane should not beconstrained. This is equivalent to saying that the coefficients a(k) andb(k) may take on any values. However, when realizing the filter viacomputer processing, the coefficients are usually part of a computerprogram and they are stored as data in ROM. Hence, the coefficients areexpressed with only a finite number of bits. In certain filterrealizations, this finite word length may lead to a spurious responsecalled a limit cycle.

The limit cycle phenomenom causes a nonrandom signal at the output ofthe digital filter system when the input signal level is near zero. Forexample, with an input signal equal to zero, a digital filter is likelyto produce a nonzero output signal if the filter is given a nonzeroinitial condition. This occurs in recursive filters due to the presenceof time delay in feedback paths and quantization of signal amplitudes toa finite number of bits. The potential for oscillations and nonlinearitygenerated by quantization cause the spurious output which, insteady-state, is designated a limit cycle. When examined closely, thisphenomenon is quite complex; however, the amplitude of the spuriousresponse can be reduced relative to full-scale signal amplitude byincreasing the number of bits used to represent the signal or, wheneverpossible, by setting a number of least significant bits to zero.

With regard to PMU 2101 of FIG. 17, this latter technique of setting thetwo least significant bits to zero is employed. The result of A/Dconversions in measurement processor 3500 is a 20-bit, 2's complementnumber of which 12 bits (11 data bits and the sign) are significant. Aseries of 20-bit numbers are passed to DSP 3600 from processor 3500 overbus 35001. A study of the filter realizations in DSP 3600, to bediscussed in detail shortly, indicated that the two least significantbits would be masked by limit cycle operation. In the measurement of lowTIP and RING currents, this masking would result in an inherentuncertainty of about 0.18 μa. To prevent this inherent error for lowcurrents, the 11 data bits are left-shifted by 2 bits, which essentiallyprovides a "pseudo-gain" of four. This insures that the two leastsignificant bits are zero. For high currents, this shifting need notoccur since the 11 data bits would already reside in the higher orderbit positions. This procedure was discussed in Section 3.2.3b as oneaspect of formatting the 12-bit A/D data into 20-bit words fortransmission to DSP 3600.

The particular digital filters utilized in the illustrative embodimentof the present invention, especially within DSP 3600, are implemented ingeneral purpose programmable signal processor (PSP) 4000 of FIG. 110.The architecture, the assembly language and uses of PSP 4000 inspecialized applications have been presented in the September, 1981issue of The Bell System Technical Journal; this issue was dedicated toan exposition of the PSP and the subject matter disclosed in that issueis incorporated herein by way of reference. However, to insure that thedetailed description of DSP 3600 is basically self-contained,information on the PSP 4000 that is particularly relevant to the digitalprocessing is included within the instant discussion. The basis for thediscussion of PSP 4000 is the block diagram shown in FIG. 115.

The input to PSP 4000 arrives as a stream of bits in serial form over DIat input buffer (IBUF) 4011 where it is assembled into a parallel bitword in I/O device 4010. This input word is then transmitted in parallelto data bus 4031 for delivery to the appropriate location in processor4000.

Data that is to form output from PSP 4000 is transmitted as aparallel-bit word over data bus 4031 to output buffer (OBUF) 4012, whereit is decomposed and sent out as bits in serial form over lead D0.

Processor 4000 may be programmed to receive inputs and transmit outputsin a number of different word lengths; for purposes of the presentinvention, this length is 20 bits and is known as extended linear data.In any case, processor 4000 generates a signal over I/O control lead IBFto indicate when the programmed number of bits have been received.

As indicated in FIG. 115, there are 128 RAM locations in memory 4040;each location stores 20-bit words. RAM 4040 is used to storeintermediate results of calculations and to store data that varies withtime.

ROM 4030, shown in phanton view in FIG. 115, is an internal 1K×16 ROMmemory. In the illustrative embodiment, only external ROM is used. LeadEXE* causes a bypass of ROM 4030 and controls external memory accesses.

Data-arithmetic unit (DAU) 4100 comprises multiplier 4110 and adder 4120which perform two's complement arithmetic. Data is transferred to andfrom DAU 4100 by way of three registers 4060(W), 4070(X) and 4080(Y).Outputs from unit 4100 are always transmitted by way of the W register4060. The contents of X register 4070 and Y register 4080 are inputs tomultiplier 4110. In addition, switch 4130 permits the contents of W tobe used in place of the contents of Y as one of the inputs to multiplier4110. This feature is useful, for example, when nth order digital filtersections are cascaded and the output of one section serves as the inputto the next section.

DAU 4100 is also capable of generating two nonlinear functions on thecontents of W or Y; these function generators are represented by block4140. One function is an absolute value generator and the other is alimiter operation.

Element 4150 in the feedback path between accumulator 4160 and adder4120 represents a scaling selector. One scale factor from a set offactors can be applied to the contents of accumulator 4160 to keepsignals within prescribed bounds.

The product of the contents of the X register and the Y or W registerproduces up to 36 bits and these bits are stored in P register 4170.Accumulating a series of products within accumulator 4160 may generatecarries, so 40 bits are provided for A register 4160. When accumulationis complete, the contents of A are transmitted to output W. Since Waccommodates only 20 bits, the 20 bits depicted in FIG. 116 areselected. FIG. 116 illustrates how the transfer of data bits through PSP4000 is accomplished.

As FIG. 116 shows, in transferring data from A to W, the 20 mostsignificant bits are transferred and 14 bits are dropped. The contentsof A can either be truncated or rounded, and the selected operation isperformed by device 4180.

An understanding as to how data is transferred, as depicted by FIG. 116,is essential to writing processing programs. For example, since thereare instructions in the assembly language to left and right-shift bits,it is possible to control the bits that are transferred.

Address-arithmetic unit (AAU) 4200 is shown in FIG. 115 as comprisingadder 4210 and fourteen registers 4221-4234. All registers 4221-4234,except register 4228 (LC), hold memory addresses or numbers related toaddresses. Register 4222 (PC) is the program counter, and it functionsin the same manner as the PC in any stored-program digital machine.Register 4223 (RX) is a memory pointer for the X register; it points toa data source. Register 4224 (RY) is similar to register RX. Register4225 (RYA) is also a Y register pointer but it points to an address inRAM 4040. Register 4226 (RD) is a destination memory pointer. Register4227 (RDA) functions like RYA. Register 4228 (LC) is a loop counter.Register 4221 (PR) is a program return register for jump instructions.Register 4229 (I), 4030 (J) and 4231 (K) are used to automaticallyincrement the contents of memory pointers associated with RX, RY and RD.Registers 4232-4234 (+1, -1, 0) are also auto-increment registers likeI, J and K.

Buffer 4002 is a multiplexed address/data bus used to access externalmemory for instructions and coefficients for the X register. Itsfunction as part of demultiplexer 3630 has been discussed with referenceto FIG. 112.

Finally, the block diagram of FIG. 115 indicates that there are fourcontrol registers, namely, registers 4013 (synchronization control orSYC), 4014 (status output or STR), 4015 (I/O controls or IOC) and 4190(arithmetic unit control or AUC). These registers are set byinstructions in the processor program to establish the bit patternsneeded to provide the desired operating mode.

With the foregoing overview, the instruction set presented in theabove-mentioned set of articles published in the Bell System TechnicalJournal, particularly on pages 1495-1497, may be readily understood andutilized by one skilled in the art to write digital signal processingprograms. As an additional aid, the following summarizes the functionsof the externally accessible leads of PSP 4000 as presented in FIG. 115:

DBS0-DBS15 (Input/Output 3-State)--bus DBS alternates betweentransmitting 10-bit addresses (DBS0-DBS9) and receiving 16-bitinstructions and X values. The data corresponding to a transmittedaddress must be placed on DBS following the output of the next address.When an address for an instruction is output, DBS15 is high.

EXE* (Output)--when combined with CLKOUT, allows the generation ofsignals used to latch addresses coming from DBS, latch data out of theexternal memory and enable data onto DBS.

EXM* (Input)--forces the use of internal ROM for instructions and Xvalues when high; when low, fetches are from external memory via DBS.

ISY (Input/Output 3-State)--indicates the start of a data transfer toIBUF. If active mode is selected, this signal is generated by PSP 4000and is an output. ISY is 3-stated whenever CTR* is high. If passive modeis selected, ISY is an input to PSP 4000 and is ignored while CTR* ishigh or while IBUF is full.

ICK (Input/Output 3-State)--used to shift data bits into IBUF. Data islatched on the rising edge of ICK. If active mode is selected, thissignal is generated by PSP 4000 and is 3-stated whenever CTR* is high.In this mode, ICK is a burst and lasts only for the duration of thetransfer. In passive mode, this signal is an input to PSP 4000 andeither burst or continuous clocks are permitted. ICK is ignored wheneverCTR* is high or IBUF is full.

DI (Input)--receives serial data for IBUF.

IBF (Output)--indicates the state of IBUF.

CTR* (Input)--enables data reception for both active and passive modes.While high, IBUF cannot be shifted and the signals ISY and ICK are in3-state if active mode is selected. If passive mode is selected, thesignals on ISY and ICK are ignored while CTR* is high.

OCK (Input/Output 3-State)--used to shift data bits out of OBUF. Data onDO changes after the falling edge OCK. If active mode is selected, thissignal is a burst clock lasting for the duration of the transfer and is3-stated whenever CTS* is high. In passive mode, it is an input andeither burst or continuous clocks are permitted. OCK is ignored wheneverCTS* is high or OBUF is empty.

DO (Output 3-State)--transmits serial data from OBUF. It is 3-statedwhenever CTS* is high.

OBE (Output)--indicates the state of OBUF. OBE is cleared when PSP 4000loads data onto OBUF and is set after the selected number of bits (8, 16or 20) have been clocked out of OBUF.

CTS* (Input)--enables data transmission. While it is high, OBUF cannotbe shifted and the signals OSY, DO and OCK are in 3-state if active modeselected. If passive mode is selected, the signals on OSY and OCK areignored while CTS* is high.

S0, S1 (Output)--these are the outputs (high or low) of bits 0 and 1 ofSTR 4014.

C0, C1 (Input)--these inputs can be tested by a program in PSP 4000.

RESET* (Input)--when low, PSP 4000 suspends all operations. When broughthigh, the program counter, IOC, AUC, STR and SYC registers are cleared.I/O is terminated and IBF and OBE are set. The first two instructionsfollowing a reset must be auxiliary.

CLKIN (Input)--provides the rate of operation of PSP 4000 from anexternal clock.

CLKOUT (Output)--used as a system clock to synchronize external devicesto DSP.

In view of the background information on the general characteristics ofdigital filters, including the need to protect against limit cycles, andthe overview of the architecture and programming properties of PSP 4000utilized to implement filters, certain ones of the filter functionsalluded to in Section 2.2.3c may now be explained.

The first filtering operation, designated DC6₋₋ SET, runs from 1 to 6 DCchannels within the duration of a sampling interval to determine the DCvalue present on each selected channel. Each channel is filtered withsix second-order sections in cascade, and the overall responsecharacteristic has a 3 dB cutoff of about 5 Hz and components areattenuated by 120 dB at 20 Hz. Separate outputs taps are available atintermediate filter points, normally at 40 dB and 80 dB at a frequencyof 20 Hz or, equivalently, at the outputs of the second and fourthsecond-order filters in the cascade. Since the device cycle rate issignificantly greater than the sampling rate, it is generally possibleto time-share one second-order filter to realize the cascade. The inputto each succeeding filter is merely the output of the preceding stage,and the input to the first stage is merely the sample sequence.

Presumably the signal undergoing filtering is a DC signal due to theprior synchronous demodulation in processor 3500. If there are nospurious AC components within the 20 Hz band, then the output from the40 dB tap should settle within the first 320 msec. A settled outputvalue is defined by a preselected number of consecutive samples havingvalues within a prescribed range. The preselected number of thepreferred embodiment is five samples and the prescribed range requireseach of the five samples to be within ±1% of one another. Tapping atintermediate outputs points in the cascaded structure generally allowsfor a rapid determination of a settled value. The 120 dB of filtering isrequired on the basis of noise constraints for worst case conditions.Since the severe noise conditions are met in only a limited number ofsituations, the intermediate tapping technique reduces processing timefor the majority of situations.

Since up to six channels may be processed in a sampling interval,separate channels have different settling times, each with a differentsettled output value. Even if one channel achieves a settled value, theother channels continue processing. If the data from these otherchannels does not settle after 320 msec., the 80 dB output tap samplesare then monitored for the next 120 msec. A final switch to the fullfilter weight occurs after 440 msec. If all channels settle before atimeout signal, a settled condition is established. DSP 3600 transmitsthis status to PMU controller 3100 and controller 3100 interrogates DSP3600 for the settled values during a scheduled activity.

In terms relating to PSP 4000, a settled value for one channel, or asettled condition when more than one channel is filtered, is indicatedby the OBE lead being dropped low. Interrogation occurs when the C1 leadis pulled low, followed by the CTS lead; both are controlled throughdata bus 31002. Once CTS is low, the output buffer is transmitted. Oncethe data is fully latched in PMU controller 3100, C1 is raised, therebyprecluding another transmission until controller 3100 is prepared toaccept the data. Even if data is not settled, PMU controller 3100 candemand outputs of the partially-filtered data and such data will betransmitted. A demand for data is transmitted via the C0 lead. After aninterrogation or a demand, the particular filtering operation ceases.

The flow diagram for the program utilized to control PSP 4000 duringDC6₋₋ SET filtering operations is depicted in FIGS. 117, 118 and 119.The actual program, in terms of the instruction set of PSP 4000, isgiven in the attached Appendix B, pages 188 through 197. (This AppendixB is the same one that appears as Appendix G in Rubin Ser. No. 399,177.In the INDEX associated with the Appendix B (pages 1004 through 1008),the program is designated "dc6₋₋ set.d" on page 1004. The suffix ".d"indicates that the program is to be executed by DSP 3600 and, inparticular, PSP 4000. Although the program is shown in source form, theprogram is converted to PSP object form and is stored in ROM associatedwith PMU controller 3100. A downloaded copy is transmitted fromcontroller 3100 to PSP 4000 by the procedure described earlier.

Another filtering operation, designated PULSE, performs an analysis onrotary dial pulses to establish the make/break pulse intervals. In lownoise environments, each dial pulse is substantially a rectangular wavewith some oscillatory behavior on the rising and falling edges due tothe transient characteristics of the loop and energy storage elements.In a noisy environment, other spurious interference components maycombine to mask pulse transitions. To mitigate false declarations ofpulse level changes in the presence of interference, a procedure hasbeen devised to focus on the fine structure of level changes while, atthe same time, maintaining data initiated by the start of a potentiallevel change. The procedure may be described as follows.

The signal composed of the dial pulses corrupted by noise is sampled ata rate significantly greater than the dial pulse rate, typically 8 kHzversus the standard 10 pulses per second for dial pulses. The samplesequence is presented to a comparator and each sample is classified aseither a high level sample or low lvel sample by comparison to athreshold. Presuming a high-to-low transition is under investigation,the sequence from the classifier is monitored for the first occurrenceof a sample classified as a low level sample. In one form of theprocedure, a first register counts the samples beginning with thisoccurrence. The first register is incremented until a predeterminednumber, typically ten, samples have maintained the same level. If thelevel maintained is a high level, a false indication of a transition hasoccurred, so the first register is reinitialized and the next indicationof a high-to-low transition is monitored. If the level maintained is alow level, a high-to-low transition is declared. The contents of thefirst counter are transferred to a second counter, the first counter isreinitialized and the second counter continues to count samples whereasthe first register begins a search for a low-to-high transition. Oncethis latter transition is declared, an estimate to the time duration ofthe high level of the pulse is provided by the contents of the secondregister less the predetermined number. Transitions are monitored andtime estimates presented to PMU controller 3100 until the pulse is fullyanalyzed or until a timeout occurs.

The source program for this procedure, in terms of the instruction setfor PSP 4000, is given in the Appendix B. In the INDEX for the AppendixB, the program is designated "pulse.d".

Another filtering function, designated COIN, is available to processsignals returned from coin phone totalizers. When a totalizer isenergized with, typically, 18 ma DC, tone bursts are propagated alongthe loop and the number of bursts correspond to the type of coindeposited in the pay phone. The amplitude of the tones returned producesbasically a ripple on the DC current and each burst may last between 20and 150 msec. If the composite signal of tone plus DC is applieddirectly to a bandpass filter centered at the tone frequency, thetransient effects of the large DC component oftentimes masks the minuteAC within the time required for detection and, consequently,inconsistent detection results may be produced. To mitigate this, thefollowing procedure has been developed.

Since it is known that approximately 18 ma DC is applied to a loop forcoin testing (Section 3.2.1e), and the processing is to be effecteddigitally, a low-pass digitial filter is pre-loaded at its internalnodes with the samples necessary to produce the presumed value of 18 maDC at the output of the filter. Thus, the filter generates sequenceelements as if 18 ma DC had been flowing for a considerable period andsteady-state was reached. Now the actual sequence of input samples,obtained by sampling the composite signal at a rate at least twice thehighest frequency of said tone, is presented to the low-pass filter. Inaddition, the output of the filter is also subtracted from the inputsequence and the difference sequence is presented to a digital bandpassfilter. Because of the preloading, the first and subsequent sequenceelements emanating from the low-pass filter may be utilized withoutwaiting for the low-pass filter to settle. For instance, if the DCapplied to the loop is exactly the value stored as samples in thelow-pass filter, the output from the subtraction operation is merely thetone bursts commencing with the first sample. On the other hand, if theDC on the loop is not exactly the value used to establish the non-zeroinitial conditions in the low-pass filter, the differencing operationreduces the DC from an unmanageable value to a tolerable value, eveninitially, and as the sampling operation unfolds, the output of thelow-pass filter converges to the DC level of the input sequence. Thus,after the transient response time of the low-pass filter, the output ofthe subtraction operation is the sequence of tone bursts.

The actual detection operation is completed at the output of thebandpass filter. The resultant sequence from this filter is squared andthen filtered with another digital low-pass filter to obtain a sequenceof positive values whenever the tone is present. These sequence elementsare then compared to a threshold, and if a preselected number ofconsecutive samples are above the threshold, the tone is declared aspresent.

Since it is possible that other spurious signals, particularly thosehaving frequency components within the band of the bandpass filter,other precautions must be taken to preclude false indications. Theseprecautions are similar to those devised for the PULSE technique, thatis, false indications are basically precluded by monitoring for eventsthat are defined when a predetermined number of consecutive samples havesimilar characteristics, such as all attaining a threshold value. Forinstance, to declare a 2200 Hz tone as being present, 72 consecutivesamples at a 6 kHz sampling rate must be above the threshold. Moreover,to declare an interval of "no tone", 36 consecutive samples must liebelow the threshold.

The source program for the coin phone checking procedure is given to theAppendix B and is entitled "coin.d". The flow chart for the routine isgiven in FIGS. 120 and 123.

The other PSP 4000 programs are listed in the INDEX as "bnd2₋₋ smp.d","broad.d", "dc6₋₋ smp.d", "mag₋₋ set.d" and "peak.d"; these correspondto to the descriptions of the program functions listed under Section2.2.3c as items (4), (6), (2), (3), and (5), respectively.

Listings of the programs for operating the microprocessor within theillustrative embodiment of PMU controller 3100 are also included as partof the Appendix B. Again, the same format of Appendices A, B and C ofRubin Ser. No. 399,177 is utilized to present the information for theprograms operating the microprocessor within controller 3100.

3.2.4. Loop Connection Circuitry

In Section 2.2.4, a procedure for establishing an interactivecommunication path between a maintenance administrator and a customerselected by the administrator was discussed with reference to FIG. 11.In particular, the interaction of LTS controller 2000 and portcontroller 2200 was exemplified with respect to equipment access network2700 and its associated port circuitry comprising P control section2702, busy/speech detector 2600, trunk dialer 2650, port circuits2801-2816 and sleeve lead control 2950, as well as the loop circuitrycomprising L control section 2701, talk circuits 2301-2306, DDD circuit2400 and ringing circuit 2500. The pertinent characteristics of the portcircuitry and the loop circuitry required to sequence through theoperation, from initiation to completion, may be readily ascertained byone skilled in the art since each component, by itself, has a well-knownform in the telephone industry. In fact, the arrangement comprising EAN2700 with P control section 2702 and the port circuitry is basically thesame form utilized in loop testing frames 250,251 of the standard systemdescribed in the Background Section with reference to FIG. 1. Theconnection of port circuitry to EAN 2700 and the operation of P controlsection was discussed in some detail with reference to FIG. 27.

In the MLT system, the standard arrangement has been augmented toprovide the capability of independent, therefore concurrent, access toloops connected via port circuits 2801-2816. This augmentation iseffected primarily by L control section 2701 as directed by LTScontroller 2000. L section 2701 serves the same basic function as Psection 2702; in the illustrative embodiment, each section energizesrelays which control crosspoints. A talk circuit 2301, . . . , or 2306provides the capability of establishing a call over the national dialnetwork, via DDD path 932 of FIG. 11, under control of LTS controller2000 directly and, indirectly, from user interface 230,231. Each talkcircuit is adapted to receive DDD circuit 2400 and ringing distributorcircuit 2500 as inputs. The former circuit actually places the call tothe maintenance administrator, via dial pulsing or multifrequencysignaling, whereas the latter circuit may be directed to ring anaccessed customer loop through ports 2801-2816. Again, circuits 2400 and2500 are directed by LTS controller 2000.

3.3 EE System Considerations

The control software for the MLT system resides in FE computers 220,221of FIG. 2 and this software provides high level traffic and algorithmiccontrol of the testing process by deciding which tests are to executeand by analyzing the results of the tests. In addition, the controlsoftware provides the interface to users, via devices 230,231, and linerecords stored in computer 200.

In the illustrative embodiment, the MLT controller software (MLT₋₋CNTLER) executes on a Digital Equipment Corporation PDP 11/70 Computer.PDP is a registered trademark of the Digital Equipment Corporation. Upto twelve 11/70 computers are furnished with this software and thesecomputers are interconnected via Parallel Communication Link 210. Someof these computers may serve as backup machines. The program utilized toconfigure and operate the illustrative EE computer system are listed inAppendix H of Rubin Ser. No. 399,177. These programs execute under theUNIX operating system. UNIX is a trademark of Bell TelephoneLaboratories, Incorporated.

Two types of user interfaces 230,231 are supported by this particularsoftware. These include a Teletype terminal Mod 40/4 or 4540 and aportable dial-up terminal having ASCII/Async/300 baud characteristics.Teletype is a registered trademark of the Teletype Corporation.

While the invention has been shown and described with reference to anillustrative embodiment thereof, it will be understood by those skilledin the art that changes in form and detail may be made therein withoutdeparting from the spirit and scope of the invention.

What is claimed is:
 1. A method for determining if a signal comprising asubstantially rectangular wave degraded by interference has completed atransition from its first level to its second level and for estimatingthe time spent at said second level, said signal being sampled at a ratesignificantly greater than the rate of said wave and the highestfrequency of said interference to produce a sequence of samples andwherein each of said samples has been classified as a first level sampleor a second level sample by comparison to a preselected threshold, saidmethod comprising the steps of(A) providing a monitor value initializedto said second level and a restart value initialized to said firstlevel, (B) monitoring said sequence for said monitor value and, upondetection, counting the number of samples generated until apredetermined number of consecutive samples have attained one of saidlevels, and once step (B) is entered from step (D), also incrementing anindex until said number of consecutive samples have attained one of saidlevels, (C) if said one of said levels is said restart value, returningto step (B), and (D) if this step is entered for the first time,retaining the counted number of samples from step (B) as said index,interchanging said monitor value with said restart value and returningto step (B); otherwise, indicating the presence of said transition andproviding said estimate in proportion to said index less saidpredetermined number.
 2. A method for determining if a signal comprisinga substantially rectangular wave corrupted by noise has switched from afirst level to a second level and for providing an estimate of the timeinterval of said second level, said signal sampled at a ratesignificantly greater than the frequency of said wave to produce aseries of samples and wherein each of said samples has been classifiedas a first level sample or a second level sample by comparison to apreselected threshold, said method comprising the steps of(A) providinginitialized first and second registers and monitor and restartparameters initialized to said second and first levels, respectively,(B) monitoring said sequence for said monitor parameter and, oncedetected, retaining in said first register the number of said samplesproduced until a predetermined number of consecutive samples are at oneof said levels and, once this step is entered from step (E), alsoincrementing said second register from the start of step (B), (C) ifsaid one of said levels is said retart parameter, reinitializing saidfirst register and returning to step (B), (D) if said second registerdiffers from its initialized value, transferring to step (F), (E)transferring the contents of said first register to said secondregister, reinitializing said first register, interchanging said monitorparameter and said retart parameter and returning to step (B), and (F)indicating a switched state for said wave and reporting said estimate asthe difference between the contents of said second register and saidpredetermined number times the sampling interval.
 3. A method fordetermining if a signal comprising a substantially rectangular wavedegraded by interference has changed from a first level to a secondlevel and for estimating the time period of said second level, saidmethod comprising the steps of(A) providing initialized first and secondregisters, a monitor value initialized to said second level and arestart value initialized to said first level, (B) sampling said signalat a rate significantly in excess of the frequency of said rectangularwave to provide a sequence of samples, (C) classifying each of saidsamples as a first level sample or a second level sample by comparingeach of said samples to a threshold, (D) monitoring said sequence forsaid monitor value and, once detected, retaining in said first registerthe number of samples generated until a predetermined number ofconsecutive samples achieve one of said levels, and once this step isentered from step (H), also incrementing said second register by thenumber of samples generated until said predetermined number achieve saidone of said levels, (E) if said one of said levels is said restartvalue, reinitializing said first register and returning to step (D) (F)if said second register differs from its initialized value, transferringto step (H) (G) transferring the contents of said first register to saidsecond register, reinitializing said first register, interchanging saidmonitor value with said restart value and returning to step (D), and (H)indicating the presence of said change and providing said estimate asproportional to the second register contents minus said predeterminednumber.
 4. A method for determining if a signal comprising asubstantially rectangular wave degraded by interference has changed froma first level to a second level and for estimating the time period ofsaid second level, said method comprising the steps of(A) providing amonitor value initialized to said second level and a restart valueinitialized to said first level, (B) sampling said signal at a ratesignificantly in excess of the frequency of said rectangular wave toprovide a sequence of samples, (C) classifying each of said samples as afirst level sample or a second level sample by comparing each of saidsamples to a threshold, (D) monitoring said sequence for said monitorvalue and, once detected, counting the number of said samples generateduntil a predetermined number of consecutive samples have achieved one ofsaid levels, and once this step is entered from step (F), alsoincrementing an index until said number of consecutive samples haveachieved said one of said levels, (E) if said one of said levels is saidrestart value, returning to step (D) (F) if this step is entered for thefirst time, retaining the counted number of samples as said index,interchanging said monitor value with said restart value and returningto step (D); otherwise, proceeding with step (G), and (G) indicating thepresence of said change and providing said estimated as proportional tosaid index less said predetermined number.
 5. In a system comprisingsampling means and first and second registers, a method for determiningif a signal composed of a substantially rectangular wave plus aninterference component has completed a first level to second leveltransition and for estimating the time duration of said second level,said method comprising the steps of(A) initializing said registers, (B)sampling said signal with said sampling means at a rate appreciablygreater than the frequency of said rectangular wave to provide asequence of samples, (C) comparing each of said samples with a thresholdto classify each said sample as a first level sample or a second levelsample, (D) monitoring said sequence for a second level sample, and oncedetected, counting and storing in said first register the number ofsamples until a predetermined number of consecutive samples havemaintained one of said levels, (E) if said one of said levels is saidfirst level, reinitializing said first register and returning to step(D) (F) transferring the contents of said first register into saidsecond register and reinitializing said first register, (G) continuingto count the number of samples in said sequence with said secondregister while monitoring said sequence for a first level sample, andonce detected, counting and storing in said first register the number ofsamples until a preselected number of consecutive samples have attainedone of said levels, (H) if said one of said levels is said secondlevels, reinitializing said first register and returning to step (G),and (I) indicating the occurrence of said transition and providing saidestimate as proportional to the contents of said second register lessthe contents of said first register.
 6. A method for deciding if asignal comprising a composite of a rectangular wave and interferencecomponents has changed from its first level to its second level and forestimating the time duration of said second level, said methodcomprising the steps of(A) providing a first register initialized tosaid second level, a second register initialized to said first level,and first and second counters, (B) sampling said signal at a ratesignificantly greater than the frequency of said wave and saidcomponents to provide a series of samples, (C) classifying each of saidsamples as a first level or a second level sample by comparison to athreshold, (D) monitoring said sequence for a level contained in saidfirst register and, upon detection, counting with said first counter thenumber of samples generated until a predetermined number of consecutivesamples attain one of said levels, and once this step is entered fromstep (H), also incrementing said second counter by the number of samplesgenerated from the start of step (D), (E) if said one of said levels isthe level contained in said second register, restarting said firstcounter and returning to step (D) (F) if this step is entered for thesecond time, jumping to step (H), (G) transferring the contents of saidfirst counter to said second counter, restarting said first counter,interchanging the values in said first and second registers andreturning to step (D), and (H) indicating the presence of said levelchange and presenting said estimate as proportional to the contents ofthe second counter less said predetermined number.